Methods and systems for launching tranverse magnetic waves using data-carrying arrestor

ABSTRACT

Methods and systems capable of launching signal-carrying transverse electromagnetic waves onto a transmission line in the higher voltage region of the transmission distribution network. Such methods and systems may include a surface wave launcher located in the higher voltage region, a network unit located in a lower voltage region, and an arrester separating the surface wave launcher and the network unit, the arrester preventing voltage from arcing over from the higher voltage region to the lower voltage region where the arrester provides the signal to the surface wave launcher.

CROSS REFERENCE TO RELATED APPLICATIONS

This application is a continuation of U.S. patent application Ser. No.16/813,384 filed Mar. 9, 2020, which claims the benefit of priorityunder 35 U.S.C. § 119(e) to provisional application Ser. No. 62/815,072filed on Mar. 7, 2019, the contents of both incorporated by referenceherein.

BACKGROUND

Systems and methods that communicate radio frequency (RF) signals fromone location to another have historically used one of two alternativemethods of electromagnetic wave propagation. First, RF signals may bepropagated over a wired connection, such as a coaxial cable, an opticalcable, etc. Such wired systems are used not only to communicate signalsover short distances, such as audio or video signals communicatedbetween components of stereo or other electronic equipment in closeproximity to each other, but also to communicate over very largedistances, such as the delivery of cable television and/or Internetcontent as well as telephone or other data services to large groups ofcustomers. In this latter instance, telephone or cable television (CATV)networks often provide the architecture for a multitude of wiredcommunications services used by both residential and business customersin the area, e.g. Internet, Voice-over-IP, Video on Demand, etc. Becausefiber optical systems are capable of much greater bandwidth than legacycopper coaxial wiring, while also transmitting over longer distances,most wired telecommunications networks today have replaced at least aportion of the historical coaxial copper network with fiber-opticequipment.

Second, electromagnetic waves may be propagated wirelessly from atransmitting antenna to a receiving antenna, and these waves may bemodulated to communicate a desired signal. Wireless RF communication isused in many applications, including AM/FM radio broadcasting, satellitebroadcasting, television broadcasting, cell phone communication, radarsystems, computer and mobile platform networks, remote control ofdevices, remote metering/monitoring, and many more such applications.While extraordinarily useful in such applications, many impedimentsexist to further expansion of wireless communications technologies. Forexample, wireless signals are subject to mutual interference, and aswireless transmission has become more ubiquitous, potential interferencemust be addressed with a combination of sophisticated signal processingtechniques that add to the complexity of wireless communication systems.Moreover, when power is radiated from an antenna, very little of ittypically reaches the receiver—a phenomenon known as path loss—which iscountered at the expense of increased transmit power, specializedantennas, and other burdensome solutions.

In order to accommodate growing demand for wireless services, whereconsumers desire mobile access to bandwidth-intensive services such asvideo and high-speed Internet, wireless network providers have built outsmall cell networks that are in turn connected to wired RFcommunications networks that deliver content to and from the Internetover fiber optic/coaxial lines. In this architecture, the mobile clientcommunicates with a network of cell towers, each of which in turncommunicate with a wired communications architecture, such as a HybridFiber Coaxial (HFC) network of a cable television (CATV) provider. Thislatter exchange is typically referred to as the “backhaul” portion of acellular communications network.

Still, consumer data usage is increasing at rates that are overwhelmingmicrocell base stations and existing wireless infrastructures, creatinga bottleneck of traffic as it exchanged with the backhaul portion of thenetwork. Though this bottleneck may in some instances be alleviated byexpanding wireless infrastructures, in many geographic regionsinstalling communications infrastructure is prohibitive due to lowpopulation density and topographical barriers. Thus, improved systemsand methods for transmitting data services to consumers is desired.

BRIEF DESCRIPTION OF THE DRAWINGS

FIG. 1 shows transverse magnetic (TM) wave devices that may emit andreceive data signals over the power lines.

FIG. 2A shows an exemplary TM device in accordance with one or moreembodiments of this disclosure.

FIG. 2B shows a cross-section of a TM signal from a perspective lookinginto the bore of a transmission line or cable.

FIG. 2C shows a magnetic field strength around a transmission mediumplotted against a distance from the outside of the transmission medium.

FIG. 2D shows a transverse electromagnetic (TEM) mode for a signalpropagating in free space.

FIG. 2E shows a TEM mode for a signal propagating in a coaxial cable.

FIG. 2F shows a TM mode signal propagating in a coaxial cable.

FIG. 2G shows a TM mode signal propagating as a guided wave along asingle wire.

FIG. 2H shows energy loss as a function of frequency for both the TEMmode and the TM mode.

FIG. 3A shows an exemplary TM wave transceiver having a reflector and acoupler.

FIG. 3B shows a shielded conductor connection connected to a reflectorand coupler in the TM wave transceiver.

FIG. 3C shows the electric current excitation between the reflector andcoupler in a TM wave transceiver by the transmissions via a coaxconnection to the coupler in the TM wave transceiver.

FIG. 3D shows relative geometries between the reflector and coupler in aTM wave transceiver have.

FIG. 3E shows a reflector/coupler embodiment paired in a 2:1 ratio.

FIG. 3F shows a reflector/coupler embodiment paired in a 1:2 ratio.

FIG. 3G shows a reflector/coupler embodiment paired in a 2:2 ratio.

FIG. 4A shows a network unit, which may be communicably coupled to anetwork connection.

FIG. 4B shows a larger network of utility poles with network boxes,access points, and repeaters depicted at various points within thenetwork.

FIG. 5 shows a simplified system for amplifying full duplex signals.

FIG. 6A shows an exemplary dual switched amplifier.

FIG. 6B shows exemplary control signals included at a lower frequencyspectrum from the data transmission band.

FIG. 6C shows exemplary control signals included at a higher frequencyspectrum from the data transmission band.

FIG. 6D shows an exemplary bi-directional switched amplifier.

FIG. 7 shows an exemplary arrester.

FIG. 8 shows an exemplary arrester that includes one or more metal oxidevaristors (MOV).

FIG. 9A shows an exemplary arrester that includes two or more concentricMOVs.

FIG. 9B shows an exemplary arrester that includes two or more MOVsenclosed by separate external bodies.

FIG. 9C shows an exemplary arrester that includes two or more MOVsenclosed by the same external body.

FIG. 10 shows an exemplary special-purpose computer system configuredwith a switched amplifier according to one embodiment.

DETAILED DESCRIPTION

Described herein are systems and methods for transmitting data. In thefollowing description, for purposes of explanation, numerous examplesand specific details are set forth in order to provide a thoroughunderstanding of some embodiments. Some embodiments as defined by theclaims may include some or all the features in these examples alone orin combination with other features described below and may furtherinclude modifications and equivalents of the features and conceptsdescribed herein.

FIG. 1 shows an exemplary power distribution system 100 that may includecomponents for power generation, transmission, and delivery. The powerdistribution system 100 may include a high voltage segment 102, adistribution medium voltage segment 104, and a service low voltagesegment 106. Some common components found in a power distribution systemare shown by way of illustration in FIG. 1, including a high voltagetransmission tower 108, high voltage power lines 110, substation 112with substation distribution transformer (DT) 113, medium voltage powercables 114(a), 114(b) . . . 114(n), utility poles 116, localdistribution transformer 118, transverse magnetic wave devices 119 a,119 b, 119 c, low voltage power lines 120, meter 122, and a low voltagepremises network or end user 124.

As shown in FIG. 1, high voltage transmissions may originate from apower source such as high voltage transmission tower 108 fortransmission over high voltage transmission lines 110. The power source108 may distribute long distance transmission on high voltagetransmission lines 110 to one or more substations 112 with substationtransformers 113, which then each transmit over medium voltage powercables 114. Medium voltage power cables 114 may distribute electricalpower to residential neighborhoods, commercial areas, industrial areas,or other areas where such power lines reach. The power distributionsystem 100 may use one or more local transformers 118 along utilitypoles 116 in the distribution medium voltage segment 104 to ultimatelydistribute power over low voltage power lines to end users 124.

Transformers 113, 118 are often referred to as step down transformers,because they “step down” the input voltage to some lower voltage.Transformers, therefore, provide voltage conversion for the powerdistribution system 100. For example, when power is carried from asubstation distribution transformer 113 to a distribution transformer118, power may first be converted for transmission from high voltage tomedium voltage at the transform substation 113 for transmission overmedium voltage power lines, and then converted at the distributiontransformer 118 from medium voltage to low voltage for transmission overlow voltage power lines 120 to the low voltage systems, which mayinclude end users such as 124. Such power distribution system 100 mayenable power to be carried from the distribution transformer 118 to thecustomer premises 124 via the one or more low voltage power lines 120.The local distribution transformers 118 typically feed anywhere from oneto ten customer premises 124, depending upon the concentration of thecustomer premises 124 in a particular region. The local distributiontransformers 118 may be distributed based on a number of customers to beserviced and may be installed in locations along the power distributionsystem, such as pole-top transformers located on a utility pole as shownin FIG. 1, pad-mounted transformers located on the ground, ortransformers located under ground level.

Power distribution systems include numerous segments related to power atdifferent voltages. In the United States, the power distribution mayinclude an extra-high voltage segment (not shown) including systemvoltages in the range of 230 kV-1100 kV. The high voltage segment 102may use power over the power lines in range of 69 kilovolts (kV) to 230kV. The distribution medium voltage segment 104 distributes power in therange of 600V to 69 kV. The segments of the power distribution system100 that are connected to the customers premises typically are servicelow voltage segments 106 having a voltage under 600 V between 100 volts(V) and 240V, depending on the system. It should be understood, however,that such ranges may vary by region/country, and disclosed herein aretechniques that are operable over different ranges of voltage anddifferent cable diameters. As disclosed, embodiments are described thatare operable independent of the power or voltage on the power lines,including embodiments that are passive. Also described are embodimentsthat are designed to accommodate the power lines, e.g., using certainmaterials to avoid contact voltages and short circuits.

For simplicity, FIG. 1 does not depict all components in a powerdistribution system, but highlights certain components that may be usedto implement a power line communication system. Thus, it should beunderstood that FIG. 1 does not include all components that enable apower distribution system or a power line communication system, asaspects of conventional power distribution and power line systems areknown.

As described above, the transition from one segment to another typicallyis accomplished with a transformer. For example, the transition from themedium voltage segment to the low voltage segment of the powerdistribution system typically is accomplished with a distributiontransformer 118, which converts the higher voltage of the medium voltagesegment to the lower voltage of the lower voltage segment. In theservice low voltage segment, the distribution transformer 118 may beconnected to the low voltage premises 124 through a meter 122. Asdisclosed in more detail below, the distribution transformer may not bepart of the transmission using the disclosed techniques, where thesignal may bypass the distribution transformer. For example, referringto FIG. 1, the signal may travel along the power line, drop down throughan amplifier, thereby bypassing the distribution transformer and passingfrom the left of transverse magnetic device 119 b to the right oftransverse magnetic device 119 c through an amplifier or network box117. It is possible that another transverse magnetic device 119 may bepositioned in the low voltage segment, e.g., along low voltage line 119,for purposes of extending in the 110 V portion of the system. However,wireless communication is usually available in the low voltage segmentfor delivery of signals output from the transverse magnetic device 119to a customer 124, such as via 5G or Wi-Fi technologies or the like.

Power distribution systems like power distribution system 100 existthroughout many geographic regions, which provide power to customers viapower lines. With some modification, the infrastructure of the existingpower distribution systems can be used to provide data communication inaddition to power delivery, thereby forming a power line communication(PLC) system.

Power Line Communication (PLC) is a communication technology forcarrying data on conductors typically used for electric powertransmission, enabling data to be sent over existing power cables. Inother words, existing power lines that already have been deployed tomany homes and offices, can be used to carry data signals to and fromthe homes and offices. However, the standard PLC presents a two-wiresolution, and it is not practically applicable to the medium voltagepower line. In addition, standard PLC has a narrow band and a broadbandscheme, only encompassing up to 250 MHz of bandwidth, i.e. standard PLChas limited bandwidth or data rate. In contrast, the systems and methodsdisclosed in the present application can support a very high datedepending on the operating frequency range.

In this regard, FIG. 1 also illustrates repeated instances 119 a to 119c of a transverse magnetic (TM) wave device 119 (shown enlarged in FIG.2A) that may emit, receive, and relay data signals over the power lines,and embodiments for the TM device 119 are described in more detailbelow. Power line communication is also referred to as power linecarrier, mains communication, power line telecommunications (PLT), andpower line networking (PLN).

While the concept of communication using the power distribution systemmay seem straightforward, there are many technical problems that arisewhen using a power line communication system. For example, transformersused in power line systems may prevent propagation of a signal, and manypower line systems are limited to a type and thickness of cable.Moreover, most existing installed overhead power lines are not designedfor the purpose of high speed data communications and are verysusceptible to radio interference, and the quality of the transmissionpower lines, including type, age, and number of joints, may have animpact on reliability for communicating data signals. Furthermore, thereare concerns that a bi-directional communication system cannot beinstalled to the existing infrastructure and/or be installed withoutdisrupting power to customers during or after installation.Additionally, federal regulations limit the amount of radiated energy ofa power line communication system, which therefore limits the strengthof the data signal that can be injected onto power lines (especiallyoverhead power lines).

In one or more embodiments disclosed herein, communication techniques ina medium-voltage and low-voltage portion of the power distributionsystem are adapted to utilize the utility-owned infrastructure in thepower distribution network to provide a reliable and affordablecommunications channel. The disclosed communication systems, devices,and methods may be used to effectively transform the power distributionsystem into a communication infrastructure. In one or more embodiments,PLC solutions are used to connect elements in power grids, which isparticularly useful where no other reliable communication channel isavailable. In one or more embodiments disclosed herein, the data may besent while the power cables are simultaneously used for electric powertransmission or electric power distribution to customers. In one or moreembodiments disclosed herein, data may be sent while the power cablesare not energized, sending data signals regardless of whether the powerlines are energized and distributing electrical power at the same time.

As disclosed in more detail below, the power line communication systemmay include a TM wave device 119 that emits a data transmission as atransverse magnetic wave guided by an outer surface of a transmissionmedium, e.g., the medium voltage power cables 114.

FIG. 2A depicts an example transverse magnetic device 119 in accordancewith one or more embodiments of this disclosure. The transverse magneticdevice 119 may transmit, receive and/or relay signals and convert theminto TM waves for propagation along a transmission medium, such as alongthe medium voltage power cable 114 also shown in FIG. 1. The device 119is in communication with a network unit 202 via connection 240, whichreceives information from a data source. By way of example, FIG. 2Adepicts receipt of information from a network 225 over connection 230,but those of ordinary skill in the art will appreciate that any sourceof information that can deliver the signals to a component in thedisclosed transverse magnetic wave transmission system is applicable.Transmissions received and/or generated by the network unit 202 can bedirected towards devices communicably coupled to the cable 114. Forexample, network unit 202 may provide data received over the network 225in transmissions to the transceiver 119 for transmission over mediumvoltage power cable 114 using the transverse magnetic wave transceiver206.

The network unit 202 may receive a signal over connection 230 from anetwork 225 and generate a transmission based on the signal and acarrier wave. The carrier wave can be modulated by the signal, and theresulting transmission can be delivered from the network unit 202 to thetransceiver 119 via signal communication line 240. The communicationbetween the network unit 202 may be based on existing transmissionprotocols and standards, such as MoCa and Wi-Fi standards. The signalcommunication line 240 may be a waveguide or transmission line thatfacilitates transportation of the millimeter-wave band transmission fromthe network unit 202 to the transceiver 119. The network connection 240can be physical such as a fiber and/or cable, or wireless, such as Wi-Fior 5G. For example, examples herein are described where the signal is inthe form of an electromagnetic wave delivered through a coaxialconnection 240.

FIG. 2A illustrates exemplary TM device 119 having an enclosure 205 andTM wave transceiver 206. As shown in FIG. 1, the TM wave transceiver 206may be integrated with enclosure 205 for installing the TM device 119along the medium voltage power cable 114 in a power distribution system100. Generally, a transceiver is a device comprising both a transmitterand a receiver that are combined and share common circuitry or a singlehousing, such as enclosure 205. As described in more detail below, theTM wave transceiver 206 may function as a transmitter of surface wavesand as a receiver of surface waves. In some embodiments, a surface waveis a signal that propagates along a surface, such as the surface of thepower cable 114. As shown, the TM wave transceiver 206 may be positionedalong a transmission medium 114 for transmission of surface-waves alongthe medium voltage power cable 114. As used herein, the surface-lineconductor, power lines, transmission wires, wire, cables, and the likerefer to the transmission medium over which the disclosed surface wavesmay propagate, such as power cables 114. The term waveguide as usedherein may refer to a structure that conveys signals, including thetransmission medium along which a surface wave propagates (on thesurface, not inside).

Upon receipt of information via connection 240, the TM wave transceiver206 may initiate signal energy onto a conductor in a surface-wave mode.Specifically, the TM wave transceiver 206 may facilitate surface wavepropagation of a data signal along the cable 114 by emitting a magneticwave that propagates longitudinally along the surface of thetransmission medium, extending emission of millimeter-waves in the rangeof 20 GHz-300 GHz to surface communications in the 1 MHz to 1 THz range.As described in more detail below, transverse magnetic transmissions asdisclosed herein extend the system from Megahertz to Terahertz. Priorsystems did not account for radio frequency interference (RFI)considerations and the physical size of the devices, which increases indeficits below 1 GHz. The disclosed transceiver may have a highfrequency range that is dependent on cable size. When frequency rangeincreases, the transceiver dimension may decrease. But, as describedherein, a transceiver design that is too small may decrease couplingefficiency if too small in relation to the cable size. Disclosedtechniques contemplate the trade-offs to maximize efficiency.

The resulting transverse magnetic surface wave propagating along thetransmission medium 114 (in contrast to signals confined within atransmission medium) has a magnetic field that is perpendicular to thelongitudinal axis of the transmission medium, i.e., perpendicular to thedirection of propagation. FIG. 2A depicts an electromagnetic wave 209emitted from the TM wave transceiver 206 and propagating along thetransmission medium 114, generating transverse magnetic field vector (H)external to the transmission medium, i.e., perpendicular, to the generalforward direction of propagation 207. Thus, the TM wave transceiver 206may emit a wave 209 guided by the surface of the conductor and travelingalong cable 114 in a direction of propagation 207, where the wave 209 isrepresented at time T1 by a single instance of the magnetic field 208(a)that is generated as the signal propagates along the transmission medium114, another instance of the magnetic field 208(b) shown at time T2.

In one or more embodiments, a specific transverse magnetic mode or modesof transmission that generates the magnetic field with a maximumstrength at a certain distance away from the transmission mediumprovides for optimal transfer of the signal. In ideal conditions, thesame magnetic field may be generated longitudinally at each distancefrom the cable as the signal travels in the direction of propagation toits destination.

As shown in FIG. 2A, the signal 209 propagates longitudinally along thesurface of the cable with the magnetic field surrounding the cable as ittravels along the cable 114. This longitudinally-travelling TM wave,however, propagates with varying magnetic field strengths “H” existingat different distances from the surface of the transmission medium, i.e.the cable 114. FIG. 2B, for example, illustrates a cross-section of thesignal shown when looking into the bore of cable 114, with the magneticfield strength in a direction perpendicular to the direction ofpropagation, as shown by the H vectors.

The transverse magnetic wave carrying data propagates longitudinallywith varying magnetic field strengths existing at different distancesfrom the surface of the transmission medium. By way of example, FIG. 2Bdepicts example signal strengths 1, 2, 3, and 4, each representing arange of signal strength as a function of the radial distance (r) of themagnetic field from the transmission medium. Thus, the signal 209 doesnot spiral around the cable 114 or curl around the cable in the samecontext as a signal that follows the right hand-rule and spirals througha cable. Rather, the magnetic field relates to a distance away from thecable and the curve that describes the magnetic field strength, asdepicted in 2C, having a magnetic field strength that varies based onthe radial distance from the transmission medium. For example, as shownby the instances 208 a, 208 b of the magnetic field in FIG. 2 A atdifferent times T1 and T2, the magnetic field represented by fieldstrength 1 surrounds the cable at the same radial distance from thecable at T1 as T2.

Not all transverse magnetic modes generated by the TM transceiver 206will persist in the field. The guided wave modes may be determined bythe cable characteristics. For example, the relative strength of TM wavemodes may depend on the transceiver design and relative geometry oftransceiver and the cable. The structure of the modes in the guided TMwave mode 209 may be controlled by adjusting a relative amplitude andphase of power injected into the ports on the transceiver 119 orotherwise provided to the TM wave transceiver 206. As will be describedherein, other factors may influence the modes that propagate along asurface-line conductor, particularly how and which modes are propagatedalong the transmission medium. Also, energy associated with the TM wavemay be determined by a diameter and geometry of the conductor.Attenuation due to various factors of the operating environment mayoccur. For example, attenuation of the magnetic field surrounding thecable may occur due to a poor condition of the transmission medium,ineffective coupling of the signal to the transmission medium, anincreasing distance from the transmission source, a poor performance ofthe transceiver, interference on the transmission medium, decreasingsignal strength, availability of power, etc.

Disclosed herein are techniques for minimizing losses and facilitating atighter coupling of the signal 209 to the transmission medium, which maythereby, among other things, improve performance, decrease the number ofcomponents required in the power line communication system, and decreasethe needs for power. In one or more embodiments, a primary transmissionmode (or modes) may be more effectively transmitted using the disclosedtransceiver 206 having enclosure 205.

In the illustration of magnetic field strengths shown in FIG. 2B, theremay be a transverse magnetic transmission mode where radius 0 has thestrongest magnetic field strength, radius 1 has a lower magnetic fieldstrength, radius 2 has an even lower magnetic field strength, so on andso forth. Alternatively, there may be a transverse magnetic transmissionmode where radius 0 has a low magnetic field strength, radius 1 has ahigh magnetic field strength, radius 2 has a low magnetic fieldstrength, radius 3 has an even lower magnetic field strength, etc. Thus,at a smaller radial distance from the wire, the magnetic field strengthis lower than at an intermediate radial distance from the transmissionmedium 114, but at a distance greater than the intermediate radialdistance the magnetic field strength decreases. FIG. 2C represents themagnetic field strength around a transmission medium plotted against thedistance from the transmission medium, for each of the transversemagnetic transmission modes described above, where the starting point onthe axis is the surface of the transmission medium and extends to adistance from the transmission medium at which distance the magneticfield is at a low or negligible strength or as attenuated and no longerexists. Reference is made herein to the Transverse Magnetic mode due toits transmission effectiveness over longer distances.

Transverse magnetic waves 209 emitted from the TM wave transceiver 206are characterized by a magnetic strength vector (H) that is entirelyperpendicular to the direction of propagation (i.e., transversecomponent) with the electric field (E) having a component parallel tothe direction of propagation (i.e., the longitudinal component). This isin contrast to transverse electric (TE) waves, which have an electricfield entirely perpendicular to the direction of propagation, as well astransverse electromagnetic (TEM) waves used within coaxial and opencable feeders, where TEM waves are characterized by both the electricfield (E vector) and magnetic strength field (H vector) being entirelyperpendicular to the direction of propagation with, neither in thedirection of propagation.

FIGS. 2D and 2E illustrate TEM propagation of a signal through freespace and in a coaxial cable, respectively, while FIGS. 2F and 2Gillustrate TM propagation of a signal through a coaxial cable and as aguided wave along a single wire, respectively. As described above, FIGS.2D-2G depict the differences between a TEM mode where the electric fieldE and the magnetic strength field H are both always perpendicular to thedirection of propagation, versus a TM mode where only the magneticstrength field (H) is always perpendicular to the direction ofpropagation. As shown in FIGS. 2D and 2E, for a TEM mode, the electricfield E is perpendicular both to the direction of propagation and to theH field, and the magnetic field H is perpendicular both to the directionof propagation and to the E field. For a TEM mode in a coaxial cable,the electric field has a radial vector component perpendicular topropagation and to the H field, with the wave propagating between theouter conductors. The magnetic field exists in an azimuthal (angular)direction perpendicular to propagation and to the E field. However, TEMonly stays TEM if it is presented with a uniform impedance across thewave front; if the impedance is not uniform, then the propagation delayvaries across the front, causing the vectors to tilt. In the case ofusing a single wire as a waveguide, as is disclosed herein with use of aTM mode, the presence of the wire may cause a variation in impedanceacross the wavefront (unlike free space), which causes the vectors totilt, which makes the wave no longer conform with the definition of TEM.

As shown in FIG. 2G, for a wave propagating in a TM mode within acoaxial cable between the outer conductor layers, the electrical fieldhas radial and longitudinal vector components, while the magnetic fieldexists in the azimuthal (angular) direction perpendicular topropagation. FIG. 2H illustrates TM propagation of a guided wave along asingle wire and how the electric field E and magnetic strength field Hare similarly generated during wave propagation, where the electricalfield has radial and longitudinal vector components, and the magneticfield exists in the azimuthal (angular) direction perpendicular topropagation.

It is notable that in the present embodiments, the TM wave transceiver206 emits signals in one or more TM waves, in contrast to TEM wavesoccurring in a coaxial connection and having a return. Propagation of aTM wave produces a non-zero longitudinal component of the E-field, incontrast to TEM waves in coax, which produce only a transverse E-field.Thus, while many conventional systems may refer to use of a transmissionmedium or waveguide, the type of wave generated more particularlydefines the nature of the transmission medium or waveguide.

In one or more embodiments disclosed herein, the transmission medium maybe a single-wire transmission line, such as a single-line conductor, fortransmitting guided surface waves, including electrical power orsignals, using a single electrical conductor. TEM waves use a coaxialconnection having a ground connection and a return current when a signalis transmitted, and generally require at least two conductors. Incontrast, the single wire system used for transmitting TM waves does notrequire and/or include a return. As described in more detail below, asingle-wire transmission line transmits electrical power or signalsusing a single electrical conductor in contrast to a pair of wires ormultiple conductors. A single-wire transmission line differs from theuse of the earth to effectively form a second conductor because there isno second conductor of any form in a single-wire transmission system.

Propagation of a TM wave produces a non-zero longitudinal component ofthe E-field, in contrast to TEM waves in coax, which produces acompletely transverse E-field. Over a single-conductor transmissionline, such as medium voltage power line 119, transverse magnetic modes(TM) may be excited by a displacement current. Thus, while TEM waves areexcited by real current, a TM wave is excited by the displacementcurrent. In the case of TM waves, a conductor that comes near or crossesinto a boundary where the magnetic field is generated along theconductor may interfere with the transmission. For example, a nearbyconductor other than the line may provide a termination point and thusreduce energy coupled in to the transverse magnetic wave. In general,impairments have more influence on the energy loss of the transmissionthe closer the impairment is to the surface of the transmission medium.At larger distances from the signal and conductor, moving away from theboundary of the magnetic field generated by the TM wave, a conductingimpairment may have little to no impact on the magnetic field. Thus, itis desirable to minimize interference in the space around the cablethrough which the signal and resulting perpendicular magnetic fieldextends.

FIG. 2H provides an example of the relative losses incurred by TM andTEM waves, in a plot of frequency vs. loss. As shown, the TM wave hasless loss at higher frequencies. The guided wave traveling on and aroundthe guiding wires may be presented itself in different characteristicmodes, just the same as those in the traditional waveguides, where eachmode is represented by the corresponding eigenvalue and eigenfunctionsolved from wave equation and boundary conditions. The fundamental TMwave does not have a cutoff frequency, while the higher modes may havetheir specific cutoff frequencies. The transceiver design may bespecifically optimized to excite the specific modes. In general, thefundamental mode has lower transmission loss and low radiation loss. Thedisclosed transceiver device can effectively convert the RF signal intothe guided wave along the medium voltage power wires.

FIGS. 2A-2H illustrate properties of a transverse magnetic field thatsurrounds a wire, illustrating why a conductor that crosses into theboundary of where the transverse magnetic field surrounds the wire willinterfere with the signal surrounding the wire, thus causing loss on theline. Optimizing energy on the line differs for the disclosed TM wavetransmissions, influencing both geometries selected for thetransceiver's reflector and coupler, both independently and in relationto each other, and influences the enclosure used to enclose thetransceiver. TM modes may include a variety of modes, where some modescouple more efficiently to the transmission medium and others splay offin directions away from the wire. The geometries selected for thedifferent TM modes are selected for maximizing the amount of energyoutput along the transmission medium.

A primary transmission mode refers to the transverse mode tightlycoupled to the transmission medium that can effectively transmit themessage signal. While the transceiver 206 may generate a number of modesin different directions, modes that are not directed down thetransmission medium or have high losses will attenuate or dissipate. Incontrast, the primary transmission mode has lower losses and is moretightly coupled to the waveguide for propagation to a next transceiver.Many modes will not persist due to attenuation or ineffective couplingto the transmission medium. In one or more embodiments, a primarytransmission mode may be more effectively transmitted using thedisclosed transceiver 206, enclosure 205. Thus, one or more embodimentsdisclosed capitalize on the features of the transverse magnetic fieldthat is generated upon excitation of current at the coupler.

FIG. 3A illustrates an example of the transverse magnetic (TM) wavetransceiver 206, which in this example is shown with a reflector 302 anda coupler 304. As shown in FIG. 1, the TM wave transceiver 206 may beincluded in transceiver 119 that is positioned in the power linecommunication system for transmission of surface-waves along a mediumvoltage power line in the power distribution system. The TM wavetransceiver 206 may include reflector 302 and coupler 304, conductivecomponents configured as parallel planar elements in a position that isperpendicular to the transmission medium 114. The planar components arethus not coaxially aligned.

In an example illustration where the transmission medium 114 extendshorizontally in an x-direction, the reflector 302 and coupler 304 arepositioned in a plane perpendicular to the x-direction, where the planeincluding the reflector 302 and coupler 304 can rotate in any directionaround the x-axis while remaining perpendicular with respect to thetransmission medium. The coupler 304 is shown positioned to a side ofthe transmission medium rather than coaxially aligned, but it is notedthat the disclosed techniques include embodiments that may be coaxiallyaligned since the unique properties of the design may not require suchdistinction.

Referring to FIG. 3B a shielded conductor connection 306 may connect toa reflector 302 and a coupler 304. Specifically, a coaxial cable 323 isan example coaxial connection 306 that serves as a signal path totransfer signals to the TM wave transceiver 119. References are madeherein to a coaxial connection, coax cable, coax, or the like todescribe connection 306. However, it should be understood that thecoaxial terms are used by way of example and other types of shieldedconductor connections with a conductor and shield as described below mayapply, including a traditional waveguide depending on the frequenciesemployed.

The connection 306 includes a central conductor portion 320, which maybe a bare copper round wire inner conductor, solid or stranded. Thecentral conductor 320 serves as the main signal path and is electricallyconnected to coupler pin 310 on coupler 304. The central conductor 320may be surrounded by a ground shield portion 321, such as a tubulardielectric insulator, which may in turn be surrounded by a protectiveouter layer 322, such as a plastic outer layer. The shield portion 321,such as the dielectric insulator of a coax, may be configured to connectto reflector pin 308 on the reflector 302. Thus, a coaxial connection isan example of a shielded conductor path that has a shield portion 321that terminates at the reflector 302 and a central conductor portion 320that terminates at the coupler 304.

The coaxial connection 306 represents functionality of a conductor andshield, which can also be accomplished using a PCB, e.g., pores on a PCBwith a planar trace on the coaxial connector just behind the reflector.Thus, FIG. 3B is representative of how the connection is made betweenthe reflector and coupler, but a PCB with traces to the reflector andcoupler or a similar design may be operable such that the shield orreflector portion of the connector 306 is traced to the reflector and aconductor line 320 is coupled to the coupler. The outer layer 322 may bea shield or reference line.

As described in more detail below, the reflector 302 and coupler 304 maybe integrated in to an enclosure, and the enclosure may include acoaxial port and a coaxial feed port may be configured to connect thecoax to a connection point 308 on the reflector 302, such as pin 308 onthe reflector, and a connection point 310 on the coupler, such as pin310 on the coupler 304. FIG. 3B illustrates the coupler 304 centeredvertically in its connection to the coaxial line 306, but alternateembodiments are contemplated. Experimentally, a vertical connectionimproved performance, but again the geometries for the reflector andcoupler and the gap between them may impact the effectiveness ofpositioning. For example, minimizing the gap between the reflector andcoupler lessens the length of the coaxial cable 321 that is unreferencedby the shield.

As shown in FIG. 3C, the current, or signal, transmitted via the coaxconnection to the coupler in the TM wave transceiver 206 causes currentexcitation. At the coax point of excitation between the coupler andcentral conductor 320, E-fields 312 extend from the coupler and arenormal to the surface of the coupler and reflector adjacent to thecoupler, which induces a transverse magnetic field on the transmissionmedium. The energy from the excitation point at the coaxial connectionis converted into the transverse magnetic wave propagating along thecentral conductor, and the launch mode generation field is the resultingtransverse magnetic field generated by the current excitation. Thus, thecoaxial drive causes excitation on the coupler, and energy is convertedto a surface wave.

The launch mode generation field varies with the magnitude of themessage signal that excites current, resulting in propagation of thetransverse magnetic wave along the surface wave conductor. Thus, the TMwave transceiver 206 creates a transverse magnetic field external to thesurface-wave conductor that propagates along the surface of theconductor. As will be described in more detail below, multiple modes maybe generated by the TM wave transceiver 206, where the mode that is mostefficiently entrained to the line will remain in propagation, i.e.,primary transmission mode, while modes with higher losses disappear overtime.

In one or more embodiments using a single-wire system, in contrast toelectromagnetic signals that have a return on the coaxial connection,the disclosed transverse magnetic transceiver does not have a return onthe shield portion of the coaxial connection. Single wire surface modetransmission exhibits far less attenuation over frequency than coaxialcable. That is because the field surrounds the conductor and is notconstrained by either a lossy return conductor or a supportingdielectric. Thus, the single shield of the coaxial connection andcentral conductor 320 as shown in FIG. 3B may operate with asingle-ended signal.

The interaction between the reflector and coupler is important. Asdescribed in more detail below, the relative size of the reflector andcoupler are selected for improved performance. In embodiments, thecoupler's length must be equal to or greater than half of the reflectorslength in order to attain the highest throughput at a frequency range 1GHz to 1.6 GHz. However, different values for the coupler and reflectorlengths will help to optimize for various outcomes. A differential cableor two-wire interface (e.g., twisted pair) may be integrated to providetwo connections—a signal and return—to operate with a differentialsignal. However, a single-ended signal provided by the coaxialconnection may maintain the energy for the transmission by the couplerrather than splitting power between split signals. Maintaining a singlesignal may more effectively transmit a primary transmission mode in thedirection of the desired direction of propagation.

Coupling the signal to the medium voltage power line that carries themagnetic field is accomplished by positioning the reflector and coupleron or close to the transmission medium. The reflector and coupler areconstructed as a transceiver device, mostly by a planar process on adielectric substrate. The device is positioned close to the mediumvoltage power wire, either in contact or non-contact. When in contact,an insulating layer is preferably applied on the reflector and couplerto avoid direct metal-to-metal contact of the coupler or reflector withthe wire. In either case, an alignment structure may be used to bringthe optimal spatial arrangement. The conductor portion of the coax thatconnects to the coupler pin 310 is the connected structure that emitsthe signal for propagating along the surface of the transmission medium.The reflector 302 and coupler 304 are coupled to the transmission mediumclose enough that the signal emitted by the coupler connected to thecoax conductor will facilitate propagation along the surface of thetransmission medium.

As shown in FIG. 3C, the reflector 302 and coupler 304 may be configuredas described above to generate a field in just one domain. The reflectorand coupler are optimally configured to shape the magnetic fielddistribution generated by the varying E-field to match guide wave modaldistribution in the intended frequency range, which depends on thegeometry of the transceiver. The absolute length of the coupler dependson the frequency range of interest. The other dimensions, such as thelength and width of the reflector, the width of the coupler, and the gapbetween coupler and reflector can be optimized based on the wire.

The domain in which the E-field 312 may be generated using alignedreflector and coupler planes is in the vertical domain, or y-direction,where at least a portion of the field lines pass between the reflectorand coupler, in both directions. When transmitting, there is an E-fieldin the gap between the reflector 302 and the coupler 304, generated bythe source. The time variation of the E-field generates a magnetic wavethat closely matches the modal distribution of the transverse magneticwave mode of wire, thus facilitating the signal energy transfer from thetransceiver 206 to the transverse magnetic wave mode guided by the wire114 shown in FIG. 1. At a receiving transceiver 206, the guidedtransverse magnetic wave generates a corresponding E-field in the gap,which will be received. The emission of the signal from the coupler 304along the transmission medium 114, and the field created betweenelements 302 and 304, in turn generates a magnetic field that couples tothe surface-wave conductor, as described in FIG. 2, such that one ormore transverse magnetic modes are coupled to the transmission medium,or medium voltage power line. The reflector 302 and coupler 304 may beconfigured so that the magnitude of the E-field is proportionate to themagnitude of the signal to transmit.

The size and shape of the reflector 302 and coupler 304, and theirrelative shapes and sizes, may impact performance of the TM wavetransceiver. Referring to FIG. 3D to describe embodiments, R_(L) is ameasurement of length of the reflector, R_(W) is a measurement of widthof the reflector, C_(L) is a measurement of length of the coupler, andC_(W) is a measurement of width of the coupler. In some preferredembodiments, the coupler's length may be a value that is between onethat is approximately equal to length of reflector and one that isapproximately half the length of the reflector to have a high peakthroughput in our frequency band of interest (1 GHz to 1.6 GHz). Theoptimal ratio between the coupler and reflector is dependent on theapplication, and the desired balance between overall bandwidth, averageinsertion loss, minimum insertion loss, and amplitude flatness. In someembodiments, the best performance occurs when the width of the reflectorand coupler are approximately equal. As used in the specification andthe claims, the term “approximate” encompasses variations of 5% or less.

In an example of surface wave communications in a power linecommunication system, the surface waves may be millimeter-waves havingfrequency range in the magnitude of GHz, such as in a frequency rangespanning from 20 GHz-300 GHz. In one or more embodiments, the messagesignal for transmission using surface waves and the surface-waveconductor has a frequency of at least 1 GHz, which includes ultra-highfrequency and microwave electromagnetic wave signals. Wi-Fi networkstypically operate in 2.4 GHz or 5 GHz bands. There are also 60 GHzwireless network protocols developed for transmitting large amounts ofdata. The performance of the TM wave transceiver in any intendedfrequency range are dependent on the transceiver geometry and electricalproperties, as well as the physical and electrical properties of mediumvoltage power wire. These parameters include the length, width,thickness and conductivity of reflector and coupler, the dielectricconstant and the thickness of the substrate, and the wire size andconductivity of the wire. The relative position of the TM wavetransceiver and the wire is also important.

The height and/or length C_(L) of the coupler may be determined based onthe frequency of the signal to be transmitted along the surface-waveconductor, such as the TM wave transceiver 206. The height and/or lengthC_(L) may determine how effective the coupler is for transmitting at aparticular frequency. For a set of transceiver geometries (C_(L), C_(W),R_(L), R_(W)), the geometries can be scaled by a common factor in orderto scale the center frequency of the resonant passband by the inverse ofthat scaling factor. For example, if a set of transceiver geometriesresonates at a center frequency of fc, then reducing all of thetransceiver geometries by a factor two will result in doubling theresonant center frequency. Thus, the wavelength of the signals to betransmitted by the coupler may drive the length of the coupler. By wayof example, a signal having a frequency of 1 GHz may have a wavelengthof approximately 12 inches, (1 GHz has a wavelength of 30 cm, which isroughly 12 inches, where wavelength=speed oflight/frequency=2.9979×10{circumflex over ( )}8 meter/1 GHz=29.98 cm˜12inches). The coupler length may be determined relative to the wavelengthsize, such as ½ of the wavelength at 6 inches or ¼ of the wavelength at3 inches. In one or more embodiments, the length C_(L) of the coupler isequal to or less than one half-wavelength of the lowest frequency orfrequencies of the signal to be transmitted. Thus, the cutoff of thewavelength may be related to the length of the coupler. The guided TMwave along a wire may travel in the fundamental wave mode where there isno cutoff frequency. However, when the TM transceiver's performance incoupling the signal into a TM wave has well-defined band-passcharacteristics, those characteristics are not only dependent on thetransceiver design, but also dependent on the conductivity of the wireand the relative position of the transceiver to the wire, i.e. thereturn loss of the transceiver as shown by an the S11 curve differs whenit is far from the wire as opposed to when it is mounted to the wire.

Since the TM wave transceiver 206 can function as both a receiver and atransmitter, the reflector 302 may act to reflect the waveform thatpasses through the coupler 304 when receiving signals. In receive mode,the signal comes to the coupler 304, but often not all of the signal isinjected into the coupler 304. Practically, at least part of the signalpasses through the coupler, and towards the reflector.

Further, a current may be induced in the opposite direction of signaltransmission. Referring to FIG. 3 D, the transmission between pins 308,310 creates standing waves on the coupler having V_(max1) and V_(max 2)of the signal, corresponding to the top and bottom of the coupler 304,where Imax occurs in the middle of the coupler 304. A message signal 350sent between pin 308 and pin 310 is a signal within the coaxial cable,such as a TEM wave. Thus, there is naturally a return current inducedequal and opposite to the direction of signal transmission, which is howa referenced single-ended signal operates. In the case of TM wavesdescribed herein during transmission, transmission modes may be directedaway from the transmission line, thereby sending current at differentdirections from the coupler that may not be completely terminated by thereflector.

If the reflector width is too large, the signals that pass through thewide reflector may reflect off the edge of the reflector furthest fromthe coupler. For example, consider that if the message signal has manypeaks and valleys at variable heights and widths, the return currentinduced is equal and opposite to the direction of signal transmission.At the connection point between the coax and pin 308, the message signalsees the connection point as a stub, causing return current to see theback (left edge) of the reflector as a stub. Thus, it may be desirablethat the reflector size be large enough to reflect signals that passthrough the coupler when the TM wave transceiver 206 transmits orreceives along the transmission medium. However, as described above, areflector that is too large may act as a stub on the signal referenceline, such that the reference signal bounces off the back wall of thereflector and returns in the direction of transmission by the coupler,but is out of phase with the desired current.

When the return current reflects off the back (left edge) of thereflector, the reflection is out of phase and interferes with themessage signal's integrity. Thus, when a single-ended signal, incontrast to differential, is transmitted by the coupler, the referencesignal may cause ripple and narrowband disappearances in frequencyresponse, known as “suckouts,” in the signal due to currents created inthe reflections that are out of phase with the desired current, causingdestructive interference. The present inventors found that if thereflector and coupler have a length of 8 inches for the intendedfrequency range of 1 to 1.6 GHz, and when the relative ratio ofreflector length and coupler length is close to or below ½, or above 2,the coupler's performance exhibits very different characteristics. Thelength of the coupler and/or the reflector may in some embodiments beapproximately one wavelength of the intended signal frequency, but maybe finally optimized considering the characteristics of the wire and therelative position of the coupler and reflector to the wire and to eachother.

Further, a reflector that is too large may reflect the signals receivedin all directions. The reflections that are directed away from thetransmission line may be acceptable, but reflections in the direction ofthe transmission from the coupler down the transmission medium may beimpacted by large reflections. Thus, the reflector size should be smallenough that reflections are minimized. In one or more embodiments, thereflector minimizes stub length while having an adequate area toterminate the field generated by the coupler.

As described above, the TM wave transceiver 206 may generate a pluralityof TM modes, e.g., TM00 TM01 TM02, etc. where only one or a subset ofthe waves generated couple efficiently to the line, while others splayoff in directions away from the wire. Geometries of the reflector andcoupler may be selected based on a combination that puts the most energyinto the desired mode, to more efficiently energize the desired mode, orthe primary transmission mode.

In one or more embodiments the geometries of the reflector and couplerare designed to focus on creating a TM01 mode as the primarytransmission mode. As shown in FIGS. 2A-2C, the TM01 may be referencedas magnetic field with varying strengths at radial distances from thewire, in contrast to modes that are referenced inside the transmissionmedium. As described in more detail below, the wire size does not impactthe design since the TM01 mode is referenced by the surface of the wire,regardless of the wire diameter, in contrast to modes that are in thewire. Thus, the TM01 mode may be desirable in embodiments as the primarytransmission mode. In one or more embodiments, the geometries maximizenot only generating a strong TM01 which exists at varying strengths atcertain distance from the line, but also creates a peak at a certainradial distance from the line. For example, referring to FIG. 2C, thepeak of magnetic field strength occurs in space range 3, represented bya radial distance (or range of distance) from the line. Thus, in one ormore embodiments, the geometries of the reflector and coupler create amagnetic field at a distance far enough from the transmission mediumthat not only resonates at the frequency of interest for transmissionbut is physically large enough compared to the conductor to encompass apoint where we desire the magnetic field strength to be at its maximum.The coupler size may determine initially the size of the magnetic field,but the reflector size and position relative to the coupler maydetermine how much of the launch mode generation field terminates at thereflector versus an amount of reflection the magnetic field is exposedto when reflected by the reflector.

Notably, a TM01 mode that surrounds the surface-wire conductor issusceptible to conductive interference that crosses into the magneticfield propagating along the surface-wire conductor. Thus, in one or moreembodiments, the reflector and coupler may be the only conductivematerials within the device 119 or part of the TM wave transceiver 206.

Experiments were preformed to find geometries that placed the mostenergy into the mode having the least loss. In one or more embodiments,the geometries are configured to energize a primary coupling of thetransmission mode to the surface-wire conductor with the lowest lossesand the tightest coupling to the surface-wire conductor to minimizeinsertion loss in the system.

A reflector width may be selected so that reflections comprising areduced version of the original signal will be only slightly out ofphase with the message signal, thereby minimizing delays. Further, areflector length is selected to provide an adequate area to terminatethe E-field generated by the coupler, where a smaller reflector that ispositioned close to the coupler influences the E-field generated by thecoupler. The same portion of the reflector that influences the fieldgenerated between the coupler and reflector is also a portion of, oroverlaps with, the portion of the reflector that reflects return currentdirected towards the reflector.

The reflector size may be determined relative to the size of thecoupler. As shown in FIG. 3C, the E-field lines 312 may be terminated bythe reflector to direct transmissions away from the reflector and directenergy forward. Thus, the reflector 302 may terminate the coupler'ssignal, forcing signals forward and not in the reverse direction, i.e.to the left in FIG. 3. Using a reflector 302 that is longer than thecoupler (R_(L)>C_(L)) may assist in directionality of the mode oftransmission. For example, as shown in FIG. 3D, because the coupler 304is shorter in length than the reflector (C_(L)<R_(L)), the E-field linesthat extend beyond the height of the coupler 304 and/or extend from thetop or bottom of the coupler that are directed in the direction of thereflector may be terminated completely or in part by the reflector sincethe reflector extends in length past the top and bottom of the coupler.The reflector may function as a stub to E-field lines directed in thedirection of the reflector, preventing all or at least a portion of theE-field generated between the reflector and coupler from extending pastthe reflector, i.e. towards the left of the reflector in FIG. 3D. Thus,the length of the reflector (R_(L)) may be determined based on thecoupler size and how much energy to direct in the forward direction. Insome embodiments, where the E-field lines are directed from the couplertowards the reflector, the termination point of the E-field line on thereflector is at a distance of up to one half wavelength away. Thus, thewidth of the reflector must be wide enough and close enough to thecoupler to terminate the E-field lines up to be present up to ½wavelength away.

In one or more embodiments, the ratio of the width of the reflector tothe width of the coupler is 1:2 and the ratio of the length of thereflector to the length of the coupler is 1.5:1. Approximatemeasurements that were tested to have low insertion losses using theseratios were R_(L)=8.375″, R_(W)=0.5″, C_(L)=5″, and C_(W)=1″. In someembodiments, the transmission was effective with a R_(L)=8″, R_(W)=1.5″for the reflector and C_(L)=6″, C_(W)=1.5″ for the coupler. Otherembodiments are contemplated, as are different ratios of sizes. Forexample, in one or more embodiments, the ratio of the width of thereflector to the width of the coupler is 1:1 and the ratio of the lengthof the reflector to the length of the coupler is 2:1 or 1.5:1. In one ormore embodiments, the reflector is always longer than the coupler.

The reflector width may be determined based on a width that bestminimizes reflections from the coupler as a function of at least one ofthe widths of the coupler, the length of the reflector relative to thecoupler, the magnitude and location of the E-field between the reflectorand the coupler, and/or a spacing between the reflector and coupler. Inone or more embodiments, the reflector width (R_(W)) is less than thatof the coupler width (C_(W)). For example, the ratio of the width of thereflector to the width of the coupler may be x:y where x<y, so that thereflector is thinner than the coupler. A thinner reflector may be betterto minimize reflections. However, depending the length of the reflectorrelative to the coupler, the magnitude and location of the E-fieldbetween the reflector and the coupler, and/or a spacing between thereflector and coupler, a thinner reflector may not perform as well forminimizing reflections. For example, some lab results indicate that a1:1 ratio of width between the reflector and coupler results in lessloss (i.e., loss of throughput measured in dB). during transmission. Inthese one or more embodiments, the width of the reflector and couplermay be the same, while the reflector remains longer than the coupler. Inone or more embodiments, the ratio of the width of the reflector to thewidth of the coupler is x:y where y<x, so that the coupler is smallerthan the reflector. The latter scenario may induce more reflections butminimizing reflections may be acceptable under certain conditions.

In one or more embodiments, the gap G, or spacing between the reflectorand coupler, may be defined. In one or more embodiments the spacingbetween a right edge of the reflector 302 and the left edge of thecoupler 304 is less than the width of either of the reflector and/or thecoupler. In one or more embodiments, the spacing is sufficient toprevent touching between the reflector and coupler, while also less thanthe width of either the reflector and/or coupler. In one or moreembodiments, the reflector 302 and coupler 304 are positioned as closeas possibly without touching. When the gap between the two edges issmaller, the produced E-field is stronger. Thus, the spacing may bedefined as sufficient to enable influence by the reflector on theE-field generated by the coupler. In addition, the wider the gap, thegreater the length of the transmission medium that is subjected to theE-field generated by the coupler. Further, when the coupling distance tothe wire changes, the impedance match changes. Thus, the coupler sizeand signal frequencies for transmission by the coupler may determine amagnitude of the E-field, and the reflector is spaced in the proximityof the E-field. In one or more embodiments, the spacing between thereflector 302 and coupler 304 is maintained at a distance that minimizesdestructive interference between return currents that reflect off theback edge of the reflector and the primary transmission mode carryingthe signal along the surface-wire conductor.

The reflector 302 and coupler 304 may be positioned parallel to eachother, with an approximately equal spacing between a right edge of thereflector 302 and the left edge of the coupler 304, which results in amore symmetric E-field generated between the reflector 302 and coupler304, and also defines a more predictable termination of the E-field bythe reflector 302.

FIG. 3D depicts the reflector 302 and coupler 304 positioned along anaxis of symmetry. In one or more embodiments, the length of each of thereflector 302 and coupler 304 in a direction that extendsperpendicularly from the direction of the transmission line is largerthan the width of each of the reflector and coupler, respectively, thatshares or overlaps in space in the horizontal direction with thetransmission medium 114. Thus, referring to FIG. 3D to describe such oneor more embodiments, where R_(L) is a measurement of length of thereflector, R_(W) is a measurement of width of the reflector, C_(L) is ameasurement of length of the coupler, and R_(W) is a measurement ofwidth of the coupler, the reflector and coupler are configured such thatR_(L) is greater than R_(W) and C_(L) is greater than C_(W).

In one or more embodiments, the reflector 302 and/or coupler 304 arecentered on the transmission medium such that the horizontal axisdefined by the transmission line is an axis of symmetry on which thereflector 302 and/or coupler 304 are centered. As shown in FIG. 3D, thereflector 302 is centered along the axis of symmetry 301 at a halfwaypoint along the length of the reflector 302, at RL/2, where the lengthis longer than the width. Similarly, the coupler 304 may be centered onaxis of symmetry 301 at a halfway point along its length, at CL/2. Inthis embodiment, the length of the reflector 302 and/or coupler 304 thatextends above the line of symmetry is the same as the length of thereflector 302 and/or coupler 304, respectively, that extends in theopposite direction from the line of symmetry in the same plane.

While the figures depict a single reflector plane 302 and a singlecoupler plane 304, it should be understood in the context of thisdisclosure that other vertically aligned configurations of the reflectorand coupler are possible. For example, the coupler may be separated intoa coupler pair.

Referring to FIG. 3A, the reflector and coupler are communicably coupledvia pin 308 on the reflector 302 and pin 310 on the coupler 304. Thereflector 302 and coupler 304 may be configured as a reflector plane andcoupler plane, respectively, each two-dimensional with a length andwidth, or having a three-dimensional shape having a length, a width, anda thickness. As described above, the length may be longer than the widthbased on the configuration with the transmission medium.

When a data or message signal is received by the reflector 308 throughconnection 306 and the message signal is emitted through coupler 304 forpropagation along the transmission medium 114, a launch mode generationfield is generated that varies with the magnitude of the message signal.The message signal excites the transverse magnetic surface wave mode onthe transmission medium, or surface wave conductor. Thus, the TM wavetransceiver 206 creates a transverse magnetic field external to theconductor that propagates down the line as described with respect toFIG. 2A. As described in more detail below, the transverse magneticfield may propagate along the surface wave conductor to a secondtransceiver, where the second transceiver may be configured to receivethe surface wave using symmetrical components.

The figures depict squared shapes, typically rectangles, for both thereflector and coupler. It should be noted that in any of theembodiments, the corners may be rounded and not squared. Rounding thecorners may avoid the Corona affect, which occurs at high voltages andcauses high charge densities on sharp corners.

As shown in the figures, the coupler may be a continuous, single planecomponent. Similarly, the reflector may be a continuous, single planecomponent. The reflector and coupler may be paired. There are multipleembodiments of parallel elements with the reflector and coupler that canbe added to optimize the bandwidth, the overall throughput, operationalfrequency and other parameters. In one or more embodiments, thereflector and/or the coupler could be paired in different ways than whatis shown in FIG. 3A, such as 1:2 (e.g., FIG. 3E), 2:1 (e.g., FIG. 3F) or2:2 (e.g., FIG. 3G.). These configurations may be positioned in the sameplane or in some sort of three-dimensional array.

In one or more embodiments, the functionality of the TM wave transceiveris agnostic to the thickness of the transmission medium. Common powerlines in a power distribution system, also referred herein as surfacewave conductors in the context of a power line communication system,range in diameter. Typical diameters for the surface-wave conductors arefrom approximately 4 mm to 25 mm or 50 mm, thus varying widely. Thedisclosed TM wave transceiver does not require direct contact with thetransmission medium and may be affixed for transmission along thesurface-wave conductor without the need for modification to transmitalong different wire gauges.

In one or more embodiments, the coupler length must be sufficient toextend beyond both the top of the transmission medium and the bottom ofthe transmission line. Thus, the coupler length must be longer than thethickness of the transmission medium If the coupler lengths is not longenough relative to the transmission medium, the coupler and reflectormay interact in the vertical configuration along the transmission mediumas disclosed herein, without modification based on the size of thetransmission medium, such as the size/gauge of a medium voltage powerline.

In one or more embodiments, the TM wave transceiver 206 is designed forisolated or indirect contact with the transmission medium. Thetransceiver 206 is completely isolated from the transmission medium. Thecoupling is strictly through the fields and not direct metal-to-metalcontact. Thus, a direct metal-to-metal or direct current connectionbetween the TM wave transceiver and the medium voltage power lines isunnecessary. In one or more embodiments, the reflector and coupler arepositioned on, or close enough to, the transmission medium to emitsurface waves for propagation along the surface of the transmissionmedium. Thus, the TM wave transceiver 206 may emit a surface wave forpropagation along the surface-wave conductor without direct contactbetween either the reflector and/or the coupler and the medium voltagepower line.

In one or more embodiments, the disclosed TM wave transceiver 206functions on either insulated and/or non-insulated transmission mediums.This is in contrast to the well-known transmission technique known asthe Goubau line, which required insulation around the conductor. Thus,while some medium voltage power lines have a jacket providing insulationto the wire, there are many medium voltage power lines that do not haveinsulation, and one or more disclosed embodiments operate on either orboth. Using a layer of insulation on the transceiver may eliminate aneed for insulation on the wire. The insulation may prevent electricallyconnecting the transceiver to an uninsulated wire, but the insulationmay have virtually no effect on an insulated wire.

Because of the nature of a TM wave surrounding the wire, a conductivematerial in the TM wave transceiver 206 or device 119 may causeinterference or impairment with the magnetic field. In one or moreembodiments, only non-conductive materials are used in the TM wavetransceiver 206 or device 119, or at least non-conductive in the spaceoccupied by the magnetic field of the primary transmission mode(s). Inone or more embodiments, the reflector and coupler are integrated on toa printed circuit board or another non-conductive material or backplate.In one or more embodiments, the PCB includes an insulating top layerover the circuitry to isolate the TM wave transceiver 206 from thesurface-wave conductor to which it is near or otherwise affixed to. Inembodiments, a FR4 PCB board is used to provide the insulation.

As described in more detail below, the TM wave transceiver 206 may beintegrated with an enclosure that facilitates installation of the TMwave transceiver 206 on or near the power line 114. For example, thereflector and coupler (or material on which they are affixed) may beintegrated in the enclosure such that when the enclosure is installed onthe transmission medium, the reflector and coupler are positioned on orclose enough to the transmission medium to emit surface waves forpropagation along the surface of the transmission medium. The guidedtransverse wave mode travelling along the wire is guided by the wire andpresent close to the wire. Pushing the transceiver against the wire willincrease the coupling performance. The closer, the better couplingperformance.

In one or more embodiments, the reflector 302 and coupler 304 may beformed with flexible metal, such that when making contact with themedium voltage power line, it will flex to ensure close contact with thetransmission medium. However, to prevent metal-to-metal contact wherethe transmission medium is non-insulated (between reflector/coupler andthe surface-wave conductor), a non-conductive material may be insertedbetween the reflector/coupler and surface-wave conductor.

In one or more embodiments, the reflector and coupler include a form ofisolation to separate pins 308 and 310 and/or any physical connectionbetween pins 308 and 310 from the transmission medium 114. For example,a form of isolation may be overlaid directly on the reflector and/orcoupler or to a medium to which the reflector and/or coupler areaffixed.

Conductivity of the surface affects the propagation of the wave, as moreconductive surfaces provide better propagation and less dissipation. Thetransceiver's performance and the system transmission performance aredependent on the characteristics of the medium voltage power lines, suchas the geometry and conductivity. Hence, even if there is a lack ofcontrol over the characteristics of the power lines, the characteristicsof the transceiver and its associated system are preferably optimized tomaximize system performance.

FIG. 4A illustrates multiple transverse magnetic transceivers 119(a)-(e)distributed in a power line distribution system 100 for facilitatingpower line communications. It should be understood that FIG. 4A depictsan example of components distributed in a power line distribution system100, but is not exhaustive nor limiting. As will be described below,transverse magnetic wave device 119(a) is shown located on or near firstutility pole 116(a), transceivers 119(b) and 119(c) are shown on orlocated near utility pole 116(b), and transceivers 119(d) and 119(e) areshown on or located near utility pole 116(c). However, FIG. 4Arepresents a subset of what could exist in a much larger network oftransceivers and utility poles in a power distribution system.

FIG. 4A shows a network unit 202, which may be communicably coupled to anetwork connection 225, such as a microcell site. The network unit 202located in the power distribution system 102 can be connected to themicrocell site 225 via a connection 230, such as by fiber and/or cable.It should be understood that additional connections 230 may be used,such as a wireless component, either active or passive. As described inmore detail below, the network unit may be coupled to an access point204 (shown in FIG. 4B) for distributing signals to end users at customerpremises 124.

Disclosed herein are techniques for distributing data to end users thatmay be employed instead, or in addition to, fiber or physicalconnections and/or the use of antennas. Conventionally, access equipmenton a utility pole may be configured with a physical connection, such asa fiber drop 235 shown extending from the network unit 202. Whereavailable, the fiber drop may to deliver content to end users 124 (shownin FIG. 1) or to a location further downstream. However, such solutionrequires a fiber or cable installed to reach the termination point.Further, equipment on the utility pole may be integrated with an antennasystem (not shown) to provide connectivity for mobile devices. Suchantenna systems are commonly integrated into the infrastructure of thepower distribution system, with network units and antennas positioned onthe pole architecture and along the power lines, separatelycommunicating information between the microcell sites to mobile devicesthat are not located in a static position. However, antennas operate infree space and transmissions distances are limited.

As disclosed herein, the network unit 202 may be communicably coupled tothe transceiver 119 that is positioned along the power lines, thetransceiver 119 for emitting signals along the power lines present inthe power distribution system. Generally, the connection between thenetwork unit 202 and the transceiver 119 may be physical, however insome embodiments passive or active wireless connections may be used. Thetransceiver 119 can receive signals from the network unit 202 withinformation that originated in the network 225 and transmit the signalsover the power lines. For example, via network connection 230, thenetwork unit 202 may combine the network signal received from thenetwork connection 225 with a carrier-wave signal, generate atransmission, and send the transmission to transceiver 119 throughconnection 240. Transceiver 119 can launch or otherwise emit a datatransmission as a guided transverse magnetic wave on the surface of themedium voltage power line.

It is notable that antennas used for transmitting data from the networkconnection 225 to mobile end users 124 are distinguishable from thedisclosed power line communication system that uses transceivers to emitsurface-wave transmissions. For example, when radio waves encounter anantenna they are converted into electrical energy and radiate in alldirections from a center point of the antenna in space, until they arereflected or absorbed. Antennas rely on free radiation or over-the-airlinks between antennas, in contrast to the use of a transmission mediumor waveguide. As disclosed herein, surface wave transmissions thatpropagate along a conductive transmission medium use magnetic fieldshaving circular geometries to propagate along the transmission medium.In fact, as described with respect to one or more embodiments below inmore detail, a tighter coupling of the signal and thus the transversemagnetic field to the transmission medium is desirable to minimize freeradiation. Transmission in free space would prevent certain features ofthe disclosed techniques from functioning.

A device 119 on or near the utility pole can also receive a transmissionover the power lines and forward it to the network unit 202. The networkunit 202 can down-convert the transmission and forward it to a networkor to a microcell tower 255.

The device 119(a) may connect to another device 119(b)symmetrically-positioned along the same transmission medium. Thesymmetrically-positioned device 119(b) may function as a repeater bytransmitting the energy received via a transceiver 206 in the device 119to a repeater 402 and back up to another device 119(c) for continuedtransmission of the surface-wave propagation of the signal along thesurface line conductor 114.

FIG. 4B illustrates a larger network of utility poles with network boxes202, access points 204, and repeaters 402 depicted at various pointswithin the network. FIG. 4B depicts multiple transceiver devices 119,some of which initiate propagation of the surface wave signal and someof which serve as repeaters of a signal received along the surface ofthe surface conductor. As shown, the repeaters may serve to connectnetwork units with components several utility poles away for continuinga signal originated at the network unit 202 using only the transceiverdevice, repeaters and the transmission medium.

The couplers and repeaters may be connected along segments of the powerline as shown in FIG. 4B, but may also be connected through differenttypes of connections. For example, a first repeater may be connected toanother repeater via physical, fiber, Ethernet, optical, or wirelessinterfaces, as shown by connection E in FIG. 4A, which should beunderstood to represent a physical connection and/or a wireless path ofcommunication. The wireless connectivity between components in the PLCsystem, such as the wireless embodiment for connection E, may be usedwhen power line connectivity is lost between neighboring repeaters.

The repeaters 402 may be positioned in the network of electric powerlines to permit information to travel longer distances on the powerlines, enabling power line communications capability. For example, therepeater and power line exchange may include the communication of data(a signal in a digital format) between transceiver for (upstream) anddownstream communication.

In some embodiments, repeaters 402 may be mounted near an electricaldistribution transformer or similar location providing access to anelectrical power line. The distribution transformer may be locatedabove-ground or below-ground, such as suspended from a pole overhead,for example. The distribution transformer may reduce a higher voltagefrom the electrical power line to lower voltages at levels that may bedelivered to end user consumers. In some embodiments, the lower voltagesthat may be consumed by end users are voltages including and between110V-220V.

The transceiver 119 and/or repeaters 402 may include a switch to switchbetween power lines. An isolation device and/or capacitor device may beprovided before and/or after a repeater 402 in the path of upstreamcommunication and/or downstream communication. Isolation and capacitorcouplers may connect the repeaters 402 to the power line. Separatelogical networks may be created and used over the electric power lines,such as by utilizing standard protocols such as standards. Thus, thepower lines may serve to enable different services. For example, a firstservice provider may use the power lines for a backhaul connectionbetween transceivers and base stations, and a second service providermay use the power lines for a logical network for WiFi hot spots, and athird service provider may use the power lines for networking electricmeters. Each network may have bandwidth allocated for each applicationby a management system.

The transceiver 119 may be utilized by utilities for other purposes,such as to read meters, detect power outages, etc. The repeaters A mayprovide one or more interfaces, such as a fiber optic interface or anEthernet interface, that interface the transceiver 119 and/or repeaterswith external equipment, such as, for example, WiFi access points,transceiver stations, low voltage gateways, electric meters, or thelike. Thus, the repeaters A may receive communications over a powerline, including external communications, and communications overEthernet, and/or fiber.

Referring again to FIG. 4A, it is important to note that the location ofthe components used for the power communication line are subject torequirements defined by the FCC and National Electric Safety Code. Forexample, one of the most fundamental safety recommendations by theNational Electric Safety Code (NESC) is the separation of supply space(power distribution) and communications space on utility poles. Thus,consistent with current regulations of the FCC and electrical safetycodes, FIG. 4A illustrates a communication space and a supply space withrequirements as to the types of components that may exist in eitherspace.

The supply space 416 (or the electrical supply zone) is located in theuppermost area of a pole, where electrical equipment (including electricdistribution cables, transformers, and capacitors) is found. Supplyspace wiring may include different voltages, and often consists ofnon-insulated conductors. For safety reasons, the highest voltages arein the highest position on the pole. Only authorized electrical workerscan work in or above the supply space, and is also referred to as thepower company's space.

The communications space 420 is the lowest space on the pole and islocated below the supply space. Attachments in this space include cable,broadband, fiber, telephone, traffic-signal control wiring, and more.The communication space is generally the location on the utility polethat is opened up for CATV and telecom providers for installingequipment for communications.

Generally, the communication space exists below the supply space. Thecommunication space is the space where workers can work safely andpassage through or under which is safe. The supply space includes theenergized electric portion of the pole space, which poses an unsafespacer for workers. Presently, the NESC requires forty inches betweenthe lowest energized electric line and communications cables/equipment.Thus, it is generally understood that the supply space encompasses theenergized portions of the space, which is a space that can pose a dangerto workers or contractors that are working on the pole.

Some utility services have installed communications devices in thesupply space, such as placing antennas at the top of the pole, as thecommunications devices themselves may not present a danger by presencein the supply space. However, it is undesirable and often a violation ofutility industry requirements to move any supply devices in to thecommunication space due to the danger posed to anyone in the vicinity ofthe supply device, and such strict clearances defined by the industryremain the safest option.

It should be noted that there may be unused space located directly belowthe supply space and directly above the communication space, which mayexist for safety. The neutral space is specified by the NESC to protectcommunications workers from dangerous voltages and to separatecommunications conductors from electric supply conductors. As shown inFIG. 4A, the distributed transformer, for example, may be located in thesupply space.

The distance between poles may be as is conventional in a powerdistribution system. It should be understood that the one network unit202 and three utility poles 116(a)-(b) are depicted in FIG. 4A forpurposes of simplicity. By way of example, FIG. 1 depicts three mediumvoltage power lines, where one or more of the three electric power linesB may be used to enable power line communication functionality includingdata transmissions. Though connectivity via three power lines areprovided in the illustrated embodiment, any number of power lines andassociated functions with regard to the present embodiments may beemployed. In an example, there may be one or more utility poles locatedbetween the poles shown in FIG. 4A, such as additional poles betweenutility pole 116(a) and 116(b). While transceivers are shown on eachutility pole depicted in FIG. 4A, it should be understood that thenetwork of utility poles may or not each have a transceiver or othercomponents described herein. Depending on distances and a performance ofthe transceivers 119 or condition of the medium voltage power cable 114,the poles located in between may or may not have additional transceiversand equipment to facilitate the disclosed techniques. In someembodiments, the transceivers are able to emit signals along the mediumvoltage power line with enough signal strength to propagate along themedium voltage power lines such that retransmission by anothertransceiver 119 may not need to occur.

Again referring to FIG. 4B, an example of a larger network of utilitypoles and components in the power distribution system to facilitatepower line communication based on the disclosed techniques shown in FIG.3B.

Additional equipment and components may be installed or integrated towork with the disclosed power line communication system, such as thenetwork box 202 and access point 204. However, as disclosed herein,different embodiments may use the same, different, or a combination ofcomponents that work with the transceivers to facilitate power linecommunication. One network unit 202 is shown in FIG. 4B mounted to oneof the example utility poles 116, but there may be more devices mountedto the poles. Further, transceivers 119 are illustrated as positionedalong the left utility pole and right utility pole in FIG. 4B, but therecould be one or more additional poles in between that are not shown forreasons of simplicity. The additional poles may or may not also have atransceiver 119.

Amplification of the network signal may be needed when communicatedthrough power cables 114. However, when power is provided through powercables 114, the power does not need amplification. Some embodimentsprovide an amplifier in one or more repeaters 402 that amplify thenetwork signal. The network signal is routed from a transceiver 119 torepeater 402, amplified, and then routed to another transceiver 119 (orback to the same transceiver). Transceiver 119 then continues to sendthe amplified signal along power cable 114.

In some embodiments, a single power cable 114 is used to transmit bothupstream and downstream data transmissions. A time division duplex (TDD)mode may be used such that the upstream transmission and the downstreamtransmission are not processed at the same time at a repeater 402. Thedata transmission in both the upstream and the downstream directionsoccurs in the same frequency range. Thus, using diplex filters toprovide isolation between the upstream amplification path and thedownstream amplification path may not be possible. Some embodimentsprovide amplifier systems that amplify data transmissions sent throughpower cables 114 in both the upstream and downstream directions.

The use of one amplifier system to amplify the data transmissionsrequires some control to route the data transmissions through differentpaths depending on whether the data transmissions are in the upstreamdirection or the downstream direction. In some embodiments, the controlis limited to either being sent on the single power line or beinglocally generated at repeater 402.

FIG. 5 depicts a simplified system 500 for amplifying full duplexsignals according to some embodiments. System 500 includes a FDX node502, an expander 504, and subscribers 510. It will be understood thatother components of the network may be included, such as other FDX nodes502 and expanders 504 may be included. Further, although not shown, ahead end may be located upstream of FDX node 502. In some embodiments,FDX node 502 may be part of a remote physical (PHY) device that can belocated closer to the subscriber's premises, such as in a node locatedin the neighborhood where the subscribers are located. The relocatedphysical device is referred to as a remote physical device (RPD). FDXnode 502 converts packets on a digital interface, such as an Ethernetinterface received via a digital network, such as via optical fiber, toanalog signals, such as radio frequency (RF) signals, on a hybrid fibercoaxial (HFC) network. FDX node 502 sends the RF signals to modemslocated at a subscriber's premises via an analog network, such as viacoaxial cable.

Full duplex signals may include different types of traffic, such as dataand video. In the downstream direction, signals from the head end aresent through FDX node 502 toward subscribers 510 through expander 504. Agroup of subscribers may be connected to a tap 512 that providesconnections to subscribers 510. Subscribers 510 may include subscriberdevices, such as modems that receive the downstream signals and send theupstream signals. In some embodiments, the modems include cable modems,but other devices may be appreciated, such as gateways. In the upstreamdirection, subscribers 510 send upstream signals toward the head endthrough expander 504 and FDX node 502.

In the downstream direction, FDX node 502 may receive a downstreamsignal from the headend and process the downstream signal using fullduplex logic 506. As discussed above, FDX node 502 may receive packetsvia a digital network. Then, FDX node 502 sends the downstream signal toexpander 504. The downstream signal is sent via an analog network.Expander 504 then amplifies the downstream signal in the analog domain.Also, in the upstream direction, expander 504 receives upstream signalsand can amplify the upstream signals in the analog domain. Then,expander 504 sends the upstream signals towards the head end, whicheventually reach FDX node 502. The upstream signals are sent via theanalog network.

Expander 504 receives the downstream and the upstream signals in thesame frequency band, which may be a range of frequencies that includesboth the downstream and the upstream signals. In some embodiments, thedownstream and upstream signals are sent at the same time, but in otherembodiments may be sent at different times. Expander 504 may process thedownstream and upstream signals using isolation and amplification logic508, which may separate the downstream and upstream signals that aresent in the same frequency band. Isolation and amplification logic 508then can amplify the downstream signal using a first path and theupstream signal using a second path. The amplification is performed inthe analog domain while isolating the downstream signal and the upstreamsignal from one another. After amplification, expander 504 may send thedownstream signals toward subscribers 510 and send the upstream signalstoward a head end.

In some embodiments, FDX expanders 504 may replace legacy analogamplifiers in the network. The use of FDX expanders 504 allows fullduplex traffic to be sent in the network without having to replace thelegacy analog amplifiers with FDX nodes 502. Also, the connectionbetween FDX node 502 and FDX expanders 504 may be transmit analogsignals, such as radio frequency (RF) signals, that may be communicatedover a coaxial cable instead of fiber. This means that the signals inthe downstream direction from FDX node 502 to FDX expanders 504 may bein the analog domain. If fiber was used, then the communications fromFDX node 502 to another FDX node may be in the digital domain, whichwould require the coaxial cable to be replaced between two FDX nodes502.

The FDX system may use the switched amplifier as described herein.

FIGS. 6A and 6D depict different examples of switched amplifiers 600according to some embodiments. FIG. 6A includes separate upstream anddownstream amplifiers in a dual switched amplifier 600-1 and FIG. 6Dincludes a single amplifier that is switched between two directions in abi-directional switched amplifier 600-2. Both amplifiers 600-1 and 600-2may operate in a time division duplex (TDD) mode. In this example, theupstream transmission and the downstream transmission from power cables114 are not processed at the same time. In this example, the clients(e.g., subscriber devices in customer premises 124) cannot transmit orreceive at the same time and thus the TDD mode of amplifiers 600-1 and600-2 is acceptable because the upstream and downstream signals arebeing sent using TDD. Switched amplifiers 600 may be used in differenttypes of systems that transmit signals upstream and downstream in thesame frequency range.

FIG. 6A depicts an example of a dual switched amplifier 600-1 accordingto some embodiments. A master controller 601 controls operation of thesystem and dual switched amplifiers 600 within the system. In someembodiments, master controller 601 is included in network box 202. Insome examples, a data transmission channel is bidirectional and operatesin a frequency range of 1.2-1.8 GHz, but other types of datatransmission channels may be appreciated.

The system uses a separate control transmission (bidirectionaltransmission or single directional) for transmission of control signals.In some examples, the control signal channels operate from a differentfrequency from which the data transmission uses, such as 1.0-1.01 GHz.In some examples, the control channels transmit data via QuadraturePhase Shift Keying (QPSK) modulated carriers in that band. In someembodiments, the system may use multiple control channels, each at adifferent frequency. One control channel is from the master controllerto the amplifiers and the clients (downstream). In some examples, thiscontrol channel is arbitrarily placed at 1000 MHz. FIG. 6B depicts anexample of control signals that are included at a lower frequencyspectrum from the data transmission band 672 according to someembodiments. At 670, one or more control signals are included at afrequency lower than the data transmission band.

The control signals may also be included at higher frequencies. Eachclient has a control channel associated with it (upstream), placed at afrequency close to the downstream channel. FIG. 6C depicts an example ofcontrol signals that are included at a higher frequency spectrum fromthe data transmission band 672 according to some embodiments. At theportion of the frequency spectrum 674, one or more control signals areincluded at a frequency higher than the data transmission band 672. Thechannel spacing may be determined by circuit trade-offs, such as thecomplexity of any channel selection filters that might be used withinthe RF receivers and demodulators found in the master controllers,clients, and the amplifiers. Optionally, additional upstream controlchannels may be used within the amplifiers to allow for moresophisticated remote control of the amplifier operation and performancetelemetry transmission back to the master controller 601.

Both the data transmission channel and the control signal channelsfollow the same transmission path, whether it is coaxial cable or othertransmission links. The control signal channels are located outside thefrequency range of the data transmission channel. This minimizesinterference to the data transmission channel and allows for minimalinterference of the data transmission channel to the control channels.

In some embodiments, there are multiple control channels used, each at adifferent frequency. There is a control channel from master controller601 to amplifiers 600 and the clients 110. In this example, this controlchannel is arbitrarily placed at 1000 MHz Each client has a controlchannel associated with it (upstream), placed at a frequency close tothe downstream channel. The actual channel spacing is determined bycircuit trade-offs, such as the complexity of any channel selectionfilters that might be used within the RF receivers and demodulatorsfound in the master controllers 601, clients 110, and the amplifiers600. Optionally, additional upstream control channels may be used withinthe amplifiers 600 to allow for more sophisticated remote control of theamplifier operation and performance telemetry transmission back to themaster controller 601.

Referring again to FIG. 6A, at each dual switched amplifier 600-1, theamplification (e.g., RF amplification) uses an amplification system thatincludes a pair of amplifiers 606 and 608 that are connected in oppositedirections with respect to their inputs and outputs, but other amplifierconfigurations may be used. For example, the control signalconfiguration may be used with a single amplifier system discussed inFIG. 6D. Switches 604 and 608 are used to connect either one amplifierthrough a first path or the other amplifier through a second path basedon a command from the master controller 601 or the client 601. Thisallows for bi-directional transmission and amplification using a singletransmission link by using time division multiplexing. The amplifier“direction” is controlled by the master controller 601 and client 601 sothat the upstream and downstream transmission traffic is properlysynchronized and does not conflict. The use of switches 604 and 608 alsominimizes any feedback possibilities between amplifiers 600 in thesystem that could potentially degrade RF performance. Other embodimentsemploy additional switches so that a single amplifier module can beswitched between the upstream and downstream directions, reducing powerconsumption and cost as will be discussed below.

In addition to dual switched amplifiers 600 being bi-directional insignal transmission, it is operationally desirable for the actual dualswitched amplifier 600-1 to be symmetric with respect to orientation atinstallation. The examples assume symmetric dual switched amplifiers 600and will be described as such in operation, but symmetric amplifiers arenot required.

Directional couplers 602-1 and 602-2 at the input/output ports of theamplifier 600 sample the incoming channels from both directions.Additionally, when the optional control signal transmitters 614-1 and614-2 are used to transmit additional control and telemetry signals tothe master controller 601, these control signals are coupled into themain transmission line through these same directional couplers 602-1 and602-2.

RF receiver and demodulators 618-1 and 618-2 select the control signalchannels from the transmission that includes the control signal and datatransmission signal, and optionally using bandpass filters 616-1 and616-2, respectively, to filter the transmission for the control signalband. RF receiver and demodulators 618-1 and 618-2 may also recover anydatasets sent from the master controller or client interpretation andexecution by the local control system. The dataset may be sending achange direction time, duration of the change, or a request fordiagnostic information or other information, etc.

Once dual switched amplifiers 600-1 are installed into the system andthe system is powered on, one initial action is for the mastercontroller 601 to send out its control signal. The RF receivers 618-1 ineach dual switched amplifier 600-1 detect which amplifier port thecontrol signal is arriving from. Local control system 612 saves the portfor later operation.

Once the downstream direction is established, dual switched amplifiers600 are set to operate in the downstream direction. This allows controlsignals from master controller 601 to be sent to all clients 110. Mastercontroller 601 polls clients 110, which respond in random time delayedfashion to minimize transmission contention on an upstream controlsignal channel that is pre-programmed into the client. Once each client601 sends a unique identifier (ID), such as the unique manufacturingcode in each client, back to master controller 601, master controller601 then assigns a unique upstream control signal channel frequency toeach client 601 along with an ID. Once a client 601 or dual switchedamplifier 600-1 receives the ID and control signal channel frequency, itstops requesting responses. This allows for contention freecommunication in the upstream direction once initiation is complete. Asimilar approach can be used for later maintenance unit replacement orfor expansion. In a similar fashion, each dual switched amplifier 600-1that has the optional control signal transmitter 614 is assigned an IDand control signal channel frequency.

Once initialized, in operation, a local control system 612 detectscontrol signals from the master controller 601 and client 601 thatindicate which direction dual switched amplifier 600-1 should receivedata transmission signals from and send data transmission signals. Localcontrol system 612 then applies appropriate switch control signals tothe RF switches 604 and 608 to attain that state. For example, localcontrol system 612 may control switches 604 and 608 to couple theupstream signal to the upstream path and the downstream signal to thedownstream path. For example, local control system 612 controls switches604 and 608 based on whether a signal is being sent downstream orupstream. When local control system 612 detects the downstream signal isbeing sent, local control system 612 controls switches 604 and 608 tocouple the downstream signal to amplifier 606 through a first path.Similarly, when local control system 612 detects an upstream signal isbeing sent, local control system 612 controls switches 604 and 608 tocouple the upstream signal to amplifier 610 through a second path.

In the downstream direction, master controller 601 sends a controlsignal to each dual switched amplifier 600-1 and client 601 signifyingthat it is going to send downstream data transmission. Dual switchedamplifier 600-1 may receive a downstream signal at a directional coupler602. RF receiver and demodulator 618-1 in conjunction with local controlsystem 612 in the first dual switched amplifier 600-1 downstream sensesthe presence of the detected control signal and then sets the RFswitches 604 and 608 to allow downstream transmission, if they are notalready in that mode. Directional coupler 602 can then send thedownstream signal to switch 604. This allows for the amplifier 606 and608 within dual switched amplifier 600-1 to increase the amplitude ofthe downstream data transmission and control signals to a suitable levelfor overcoming the insertion loss of the transmission line (e.g., powerline). If there is more than one dual switched amplifier 600-1 betweenthe master controller and the client 601, each will sense the controlsignal and will respond the same as the first downstream dual switchedamplifier 600-1. This provides for a continuous transmission path fromthe master controller location to the client location through repeaters402 and power cables 114.

In order to account for delays in the detection of the control signaland the RF switch operation, a delay period may be built into the datatransmission initiation. Although this introduces some latency to thedata transmission, it prevents loss of data transmission signal due toswitching.

In the upstream direction, dual switched amplifier 600-1 may receive anupstream signal at a directional coupler 602-2, such as a signal sentfrom client 601. Directional coupler 602-2 can then send the upstreamsignal to local control system 612. Local control system 612 controlsswitch 608 to couple the upstream signal to amplifier 610. Amplifier 610then amplifies the signal. Local control system 612 also controls switch608 to then couple the upstream signal to directional coupler 602-1.Directional coupler 602-1 then sends the upstream signal in the upstreamdirection towards the master controller 601.

Other embodiments may include sending timing data with the controlsignals to minimize the time needed for the delay between upstream anddownstream transmission. Additionally, the optional control signaltransmitters 614 within each dual switched amplifier 600-1 can be usedin conjunction with this timing data to eliminate the associated delaycaused by waiting for one dual switched amplifier 600-1 to switch priorto the next dual switched amplifier 600-1 (or amplifiers) switching. Inthis case, the control signal transmission path essentially becomesparallel to the data transmission path and functions outside of any dualswitched amplifier RF switching. That is, control signal transmitters614 can transmit the control signals for other dual switched amplifiers600-1 while processing the downstream transmission. Other enhancementsmay include remote amplifier performance monitoring, configuration, andsystem performance parameters.

In the above configuration, two different amplifiers and paths are usedto amplify the downstream signals and the upstream signals,respectively. This uses multiple amplifiers 606 and 608, but only twoswitches 604 and 610, which may simplify the switching logic. Theupstream and downstream paths are isolated by TDD in this example.

FIG. 6D depicts an example of a bi-directional switched amplifier 600-2according to some embodiments. In bi-directional switched amplifier600-2, the same amplifier 625 is used for both the upstream anddownstream amplification, and switch poles are alternated to half duplexthe upstream and downstream signals to amplifier 625. The upstream anddownstream signal paths may share components other than amplifier 625.However, the overall path that is taken is different between theupstream and downstream. That is, the upstream path takes differentcirculator port rotations and switch poles through a first path,compared to a different second path for the downstream path.

A local detection and decision circuit changes the switch poles for eachhalf duplex time slot in which signals are being sent upstream ordownstream. In one example, the local detection and decision circuitdetects when signal power is present at either upstream or downstreaminputs (e.g., input P2 or input P1). When signal power is detected atinput P2, the local detection and decision circuit changes the switchpoles to connect input P2 to the input of amplifier 625, and output P1to the output of amplifier 625. Similarly, as another example, whensignal power is detected at input P1, the local detection and decisioncircuit changes the switch poles to connect input P1 to the input ofamplifier 625, and output P2 to the output of amplifier 625. Differentand additional coupling locations, and coupling directions, for thedetection of signal power for local switching decision may beappreciated. Described herein is one embodiment of the bi-directionalswitched amplifier 600-2, with logic gate switch control decisions madefrom signal power detections of the upstream signal. Other embodimentsnot described herein include signal power detections of the downstreamsignal, and signal power detections on both upstream and downstreamsignals, for local switching decisions. Further, other variations ondetecting the power at the inputs and performing the pole switching maybe appreciated. Also, by not detecting power at that port may inherentlydetect power at the other port or the switching logic may be configuredsuch that it is assumed power is detected at the other port. Further,the multiple amplifier system described in FIG. 6A may be use the localsignal power detection to determine which of the first path and thesecond path to use in that embodiment.

In some embodiments, the bi-directional switched amplifier 600-2receives an input signal at input P2 (e.g., the upstream direction). Theinput P2 signal is rotated clockwise by circulator 620 to thedirectional coupler 621. Circulators may be used to control the signalflow and can have three or more ports. The signal in a circulatorfollows a rotary path from one port to the next, always in the samerotational direction, clockwise, or counter-clockwise. The directionalcoupler 621 couples a small percentage of the input P2 signal to afilter 632 and detector 633. Filter 632 reduces the spurious signallevels outside of the signal bandwidth to prevent a false detection. Thebandwidth of filter 632 may be narrower than the input P2 signalbandwidth to further prevent false detections. After detector 633detects the input P2 signal, a logic 1 is output to the E input of an ORgate 636. A switch control table 642 shows that an input of E=1 at theOR gate 636 input causes the OR gate to output C=1, and each switchconnected to the OR gate output (labeled with C), changes their switchpole to the C=1 state.

The large percentage of remaining input P2 signal at coupler 621 isrotated clockwise by circulator 622 and delayed by time delay 623. Theperiod of delay is enough time for the switch poles to change to C=1state, to prevent loss of input P2 signal. Until this point, the inputP2 signal has followed a path independent of the switch pole state.

After the input P2 signal has passed through time delay 623, the localswitch control logic has made the decision to change the switch poles toC=1, and switch 624 changes to connect the input P2 to the input ofamplifier 625. The input P2 signal is amplified by amplifier 625, andthe output at the C=1 pole of switch 626 is rotated clockwise bycirculator 627 to directional coupler 628. Directional coupler 628couples a small percentage of the amplified P2 signal to filter 634 anddetector 635. Filter 634 reduces the spurious signal levels outside ofthe signal bandwidth to prevent a false detection. The bandwidth offilter 634 may be narrower than the P2 signal bandwidth to furtherprevent false detections. After detector 635 detects the amplified P2signal, a logic 1 is output to the B input of the OR gate 636. Referringto switch control table 642, a detection of B=1 makes the OR gate outputC=1, so the poles of the switches will not change from C=1 state while asignal is detected by detector 635, or detector 633 (C=B+E).

The large percentage of remaining amplified P2 signal at coupler 628 isrotated clockwise by circulator 629 to the P1 output of thebi-directional switched amplifier 600-2.

Also, any reflected signal along the path from input P2 to output P1,due to impedance discontinuity, gets rotated clockwise by circulators620, 631, 622, 627, 629, and 630, where the reflected signals areabsorbed by loads 649, 650, 648, 652, 653, 654, and the output ofamplifier 625. If switches 626, 624 are non-reflective open (e.g.,internally terminated when open), or reflective short (e.g., shorted tocommon reference potential when open), then switches 638, 639, and theirloads 650, 654, can be deleted. If switches 626, 624 are reflectiveopen, (e.g., high impedance discontinuity when open), then switches 638,639, and their loads 650, 654, can be used. The reflected signalsabsorbed by loads 649, 650, 648, 652, 653, 654, and the output ofamplifier 625, will provide low reflections at the P2 input, and P1output.

After the upstream signal is no longer applied at the input P2, detector633 and then detector 635 will detect no signal. From table 642, whenthe output of detector 633 is E=0, and then output of detector 635 isB=0, and both are applied at the inputs of OR Gate 636, the switch poleschange to their C=0 state. With the switches in C=0 pole state, an inputsignal applied at port P1 in the downstream direction will be amplifiedby amplifier 625.

When an input P1 receives an input signal in the downstream direction,the input P1 signal is rotated clockwise by circulator 629 to circulator630. Circulator 630 rotates the input P1 signal clockwise to switch 624.The signal at switch 624 is at the C=0 pole and is amplified byamplifier 625, and the output at switch 626 is the C=0 pole and isrotated by circulator 631 to circulator 620. The circulator 620 rotatesthe amplified P1 signal to the output P2 of the bi-directional switchedamplifier 600-2.

Also, any reflected signal along the path from input P1 to output P2,due to impedance discontinuity, gets rotated clockwise by circulators620, 631, 622, 627, 629, and 630, where the reflected signals areabsorbed by loads 649, 651, 648, 652, 653, 655, and the output ofamplifier 625. If switches 626, 624 are non-reflective open (e.g.,internally terminated when open), or reflective short (e.g., shorted tocommon reference potential when open), then switches 640, 641, and theirloads 651, 655, can be deleted. If switches 626, 624 are reflectiveopen, (e.g., high impedance discontinuity when open), then switches 640,641, and their loads 651, 655, can be used. The reflected signalabsorbed by loads 649, 651, 648, 652, 653, 655, and the output ofamplifier 625, will provide low reflections at the P1 input and P2output.

The circulators 622, 627, 630, 631 may be eliminated from thebi-directional switched amplifier 600-2 depicted in FIG. 6D withoutchanging the embodiment of the bi-directional switched amplifier 600-2.Eliminating circulators 622, 627, 630, 631, and retaining circulators620, 629 in the bi-directional switched amplifier 600-2 may reduce costand insertion loss. The eliminated circulators 622, 627, 630, 631 may beincluded in the bi-directional switched amplifier 600-2 to reducereflections at P1 and P2.

Gain control loops can be used for amplifier 625 to control the outputsignal level. An example automated gain control loop is shown inbi-directional switched amplifier 600-2 by using detector 647,operational amplifier 643, capacitor 645, and resistors 644, 646;however, other configurations may be appreciated, includingconfigurations when using signal detection at input/output P1 andinput/output P2 of the bi-directional switched amplifier.

FIG. 7 depicts a TM device 119 connected to a network unit 202 throughan exemplary arrester 705, which preferably includes an RC network 706comprising one or more resistors 707 and capacitors 708 surrounded by aninsulating disc 710. In some embodiments, one or more signal pathsbetween a TM wave transceiver 206 and a network unit 202 may passthrough an arrester 705. The RC network 706 of arrester 705 preferablyincludes a series of resistors and capacitors arranged in a biasingladder, thereby creating a path that reduces the higher voltage of themedium voltage power cable 114 to a lower voltage that is acceptable tothe network unit 202. For example, the signal path created by the seriesof resistors and capacitors may be a high voltage protection path and ahigh frequency bypass. The series of resistors and capacitors mayprovide a signal path between the TM wave transceiver 206 and thenetwork unit 202, and data signals may be passed between the TM wavetransceiver 206 and network unit 202 along this signal path. In someembodiments, the arrester 705 may include a ground path to ground theseries of resistors and capacitors. The insulating disc 710 may includeone or more fins 715.

The TM device 119 is preferably fashioned as an outer, roughlyegg-shaped absorptive Electromagnetic Interference (EMI) enclosure 712that surrounds a surface wave launcher comprising a coupler 304 andreflector 302 as previously described. The EMI enclosure 712 maypreferably define opposed openings by which the power line that providesthe waveguide for transmitted signals may pass. A coaxial electricalconnection 716 from the network unit 202 may pass through the arrestor705 for connection to the surface wave launcher as previously described,i.e. the center conductor of the coaxial connection 716 connected to thecoupler 304 and the shield conductor connected to the reflector 302.

In some embodiments, the network unit 202 may receive signals from, andtransmit signals to, a network side interface 720 comprising an L2/L3switch 722 having a plurality of ports 724, each port capable ofpropagating network signals, such as 5G, ENET, 10G-ENET, GPON, etc.Downstream signals, i.e. signals transmitted from a network to the TMdevice 119, are received from a respective port on the L2/L3 switch 722,directed to a MAC controller 726, and upconverted and modulated bymodule 728. The upconverted and modulated signal is then optionallyamplified by amplifier 730 and routed onto coaxial connection 716 to thearrester 305 through transmit/receive switch 734. Conversely, upstreamsignals, i.e. signals transmitted from a network to the TM device 119,are received through transmit/receive switch 734 and optionallyamplified by amplifier 732. The optionally-amplified signal is thendemodulated and down-converted at module 736, sent to MAC controller 726and output onto the network interface 720 via L2/L3 switch 724. If thenetwork unit 202 transmits and receives time-division duplexed (TDD)signals, the MAC controller 726 may operate a transmit/receivecontroller 738. The network unit 202 preferably operated usingcommercial 110 volt power.

FIG. 8 shows an exemplary arrester 805 that includes one or more MOVs(metal oxide varistors). In some embodiments, one or more signal pathsbetween a TM wave transceiver 206 and a network unit 202 may passthrough the arrester 805. The arrester 805 may include one or moresignal paths that pass through a material or circuitry through which anRF signal may be passed while withstanding high voltage and providing alow impedance path to low frequencies. For example, the arrester 805 mayinclude one or more signal paths comprising MOVs (metal oxidevaristors). The MOVs may include gapped or un-gapped MOVs. Each MOV mayinclude one or more MOV discs, wherein the number of MOV discs includedin each MOV is based upon a desired impedance.

An MOV may include granules having a capacitive connection between them,and when the voltage potential across the plates of the MOV reaches acertain value, the voltage has enough potential energy to jump over thegaps between granules. Once voltage is high enough, the voltage maycross the MOV and may be passed to ground. The one or more signal pathsof the arrester 805 may be encompassed by an external body 810. Theexternal body 810 may include one or more fins 815.

FIG. 9A depicts an exemplary arrester 905 that includes two or moreconcentric MOVs, thereby creating a coaxial connection between atransceiver (e.g., TM wave transceiver 206 of FIG. 2) and a network box(e.g., network unit 202 of FIG. 2). Each respective one of the two ormore concentric MOVs may provide a signal path between the transceiverand the network box. For example, a central or inner MOV 910 may providea signal path for a coupler (e.g., coupler 304 of FIG. 3), and an outerMOV 915 may provide a signal path for a reflector (e.g., reflector 302of FIG. 3). The central or inner MOV 910 may be shaped as a cylinder.The outer MOV 915 may be shaped as a hollow cylinder (i.e., a cylinderhaving a hollow portion), wherein the central or inner MOV 910 is placedwithin the hollow portion of the outer MOV 915.

In some embodiments, data signals may be passed along at least one ofthe one or more signal paths. In some embodiments, the arrester 905 mayhave a coaxial connector (e.g., coaxial RF connector) at both ends. Thesignal path created by the inner MOV 910 may be routed through a coaxialconnector to a center conductor (i.e., interior portion) of a coaxialcable, and the signal path created by the outer MOV 915 may be routedthrough a coaxial connector to a shield (i.e., outer portion) of thecoaxial cable.

The concentric MOVs may preferably be separated from each other by aninsulator 920, thereby separating the different signal paths. Forexample, a gap between the central or inner MOV 910 and the outer MOV915 may be filled with an insulator 920. In some embodiments, theinsulator 920 may be a hollow cylinder that is placed between thecentral or inner MOV 910 and the outer MOV 915. The two or moreconcentric MOVs may be encompassed by an external body 925. The externalbody 925 may include one or more fins 930. While the two or more MOVsare shown in FIG. 9A as being concentric, it should be understood thatthe MOVs may be configured as coplanar, twisted pairs, or otherconfigurations.

FIG. 9B shows an alternative exemplary arrester 935 that includes two ormore MOVs 940 a, 940 b that are each enclosed by separate respectiveexternal bodies 945 a and 945 b, thereby creating multiple signal pathsbetween a transceiver (e.g., TM wave transceiver 206 of FIG. 2) and anetwork box (e.g., network unit 202 of FIG. 2). Each respective one ofthe two or more MOVs 940 a, 940 b may provide a signal path between thetransceiver and the network box. Each of the two or more MOVs 940 a, 940b may be positioned beside each other, and the MOVs 940 a, 940 b may beseparated from each other by an insulator 950 a, 950 b. For example,each of the MOVs 940 a, 940 b may be encompassed by an insulatingmaterial. A first MOV (e.g., MOV 940 a) may provide a signal path for acoupler (e.g., coupler 304 of FIG. 3), and a second MOV (e.g., MOV 940b) may provide a signal path for a reflector (e.g., reflector 302 ofFIG. 3). The MOVs 940 a, 940 b may be shaped as cylinders and mayinclude one or more MOV discs. In some embodiments, data signals may bepassed along at least one of the one or more signal paths.

A signal path created by a first MOV (e.g., MOV 940 a) may be routedthrough a first terminal that is connected to a center conductor (i.e.,interior portion) of a coaxial cable passing between the arrester 935and the transceiver and through a second terminal that is connected to acenter conductor (i.e., interior portion) of a coaxial cable passingbetween the arrester 935 and the network box. A signal path created by asecond MOV (e.g., MOV 940 b) may be routed through a first terminal thatis connected to a shield (i.e., outer portion) of a coaxial cablepassing between the arrester 935 and the transceiver and through asecond terminal that is connected to a shield (i.e., outer portion) of acoaxial cable passing between the arrester 935 and the network box.

Each respective one MOV of the two or more MOVs 940 a, 940 b may beencompassed by an external body 945 a, 945 b dedicated for enclosing therespective one MOV. Therefore, the arrester 935 may comprise multipleexternal bodies 945 a, 945 b (i.e., an external body for each MOV) andeach respective one MOV of the one or more MOVs 940 a, 940 b may beseparated from one or more other MOVs by an insulator 950 a, 950 b andan external body 945 a, 945 b. Each external body 945 a, 945 b mayinclude one or more fins 955 a, 955 b.

FIG. 9C shows an alternative exemplary arrester 960 that includes two ormore MOVs 965 a, 965 b that are enclosed by the same external body 970,thereby creating multiple signal paths between a transceiver (e.g., TMwave transceiver 206 of FIG. 2) and a network box (e.g., network unit202 of FIG. 2). Each respective one of the two or more MOVs 965 a, 965 bmay provide a signal path between the transceiver and the network box.Each of the two or more MOVs 965 a, 965 b may be positioned beside eachother, and the MOVs 965 a, 965 b may be separated from each other by arespective insulator 975 a, 975 b. For example, each of the MOVs 965 a,965 b may be encompassed by an insulating material. A first MOV (e.g.,MOV 965 a) may provide a signal path for a coupler (e.g., coupler 304 ofFIG. 3), and a second MOV (e.g., MOV 965 b) may provide a signal pathfor a reflector (e.g., reflector 302 of FIG. 3). The MOVs 965 a, 965 bmay be shaped as cylinders and may include one or more MOV discs.

In some embodiments, data signals may be passed along at least one ofthe one or more signal paths. A signal path created by a first MOV(e.g., MOV 965 a) may be routed through a first terminal that isconnected to a center conductor (i.e., interior portion) of a coaxialcable passing between the arrester 960 and the transceiver and through asecond terminal that is connected to a center conductor (i.e., interiorportion) of a coaxial cable passing between the arrester 960 and thenetwork box. A signal path created by a second MOV (e.g., MOV 965 b) maybe routed through a first terminal that is connected to a shield (i.e.,outer portion) of a coaxial cable passing between the arrester 960 andthe transceiver and through a second terminal that is connected to ashield (i.e., outer portion) of a coaxial cable passing between thearrester 960 and the network box.

All of the two or more MOVs 965 a, 965 b may be encompassed by a singleexternal body 970. Therefore, the arrester 960 may include a singleexternal body 970 encompassing all of the MOVs 965 a, 965 b. Theexternal body 970 may include one or more fins 980.

Those of ordinary skill in the art will appreciate that the arrestorsdescribed herein may be mounted to a pole or directly to a launcherenclosure.

While the various arrester embodiments disclosed herein show two signalpaths, it should be understood that the arresters may include more thantwo signal paths. The various arrester embodiments described herein maycomprise more than two signal paths (e.g., more than two MOVs). Forexample, four concentric MOVs or eight separate MOVs may be utilized tosupport signal paths through four coaxial connectors (e.g., in supportof 4G communications).

While signal paths for RF signals are described herein, it should beunderstood that the signal paths provided by the various arresterembodiments may be utilized to pass signals to and from antenna situatedabove a network box (e.g., situated on top of a power pole).

FIG. 10 illustrates an example of special purpose computer systems 1000configured with a switched amplifier 600 according to one embodiment.Computer system 1000 includes a bus 1002, network interface 1004, acomputer processor 1006, a memory 1008, a storage device 1010, and adisplay 1012.

Bus 1002 may be a communication mechanism for communicating information.Computer processor 1006 may execute computer programs stored in memory1008 or storage device 1008. Any suitable programming language can beused to implement the routines of some embodiments including C, C++,Java, assembly language, etc. Different programming techniques can beemployed such as procedural or object oriented. The routines can executeon a single computer system 1000 or multiple computer systems 1000.Further, multiple computer processors 1006 may be used.

Memory 1008 may store instructions, such as source code or binary code,for performing the techniques described above. Memory 1008 may also beused for storing variables or other intermediate information duringexecution of instructions to be executed by processor 1006. Examples ofmemory 1008 include random access memory (RAM), read only memory (ROM),or both.

Storage device 1010 may also store instructions, such as source code orbinary code, for performing the techniques described above. Storagedevice 1010 may additionally store data used and manipulated by computerprocessor 1006. For example, storage device 1010 may be a database thatis accessed by computer system 1000. Other examples of storage device1010 include random access memory (RAM), read only memory (ROM), a harddrive, a magnetic disk, an optical disk, a CD-ROM, a DVD, a flashmemory, a USB memory card, or any other medium from which a computer canread.

Memory 1008 or storage device 1010 may be an example of a non-transitorycomputer-readable storage medium for use by or in connection withcomputer system 1000. The non-transitory computer-readable storagemedium contains instructions for controlling a computer system 1000 tobe configured to perform functions described by some embodiments. Theinstructions, when executed by one or more computer processors 1006, maybe configured to perform that which is described in some embodiments.

Computer system 1000 includes a display 1012 for displaying informationto a computer user. Display 1012 may display a user interface used by auser to interact with computer system 1000.

Computer system 1000 also includes a network interface 1004 to providedata communication connection over a network, such as a local areanetwork (LAN) or wide area network (WAN). Wireless networks may also beused. In any such implementation, network interface 1004 sends andreceives electrical, electromagnetic, or optical signals that carrydigital data streams representing various types of information.

Computer system 1000 can send and receive information through networkinterface 1004 across a network 1014, which may be an Intranet or theInternet. Computer system 1000 may interact with other computer systems1000 through network 1014. In some examples, client-servercommunications occur through network 1014. Also, implementations of someembodiments may be distributed across computer systems 1000 throughnetwork 1014.

Some embodiments may be implemented in a non-transitorycomputer-readable storage medium for use by or in connection with theinstruction execution system, apparatus, system, or machine. Thecomputer-readable storage medium contains instructions for controlling acomputer system to perform a method described by some embodiments. Thecomputer system may include one or more computing devices. Theinstructions, when executed by one or more computer processors, may beconfigured to perform that which is described in some embodiments.

As used in the description herein and throughout the claims that follow,“a”, “an”, and “the” includes plural references unless the contextclearly dictates otherwise. Also, as used in the description herein andthroughout the claims that follow, the meaning of “in” includes “in” and“on” unless the context clearly dictates otherwise.

The above description illustrates various embodiments along withexamples of how aspects of some embodiments may be implemented. Theabove examples and embodiments should not be deemed to be the onlyembodiments, and are presented to illustrate the flexibility andadvantages of some embodiments as defined by the following claims. Basedon the above disclosure and the following claims, other arrangements,embodiments, implementations and equivalents may be employed withoutdeparting from the scope hereof as defined by the claims.

1-20. (canceled)
 21. An arrester configured for interposition between anetwork unit that processes data communications signals and a surfacewave launcher that surrounds a high power transmission line and launchesthe communication signals on, and receives the communications signalsfrom the high power transmission line, the arrestor comprising at leastone metal oxide varistor (MOV) capable of preventing voltage from arcingfrom the power transmission line to the network unit, and also capableof propagating the communications signals between the network unit andthe surface wave launcher.
 22. The arrester of claim 21 comprising abiasing ladder of resistors and capacitors surrounded by insulatingdiscs.
 23. The arrester of claim 21 comprising a coaxial transmissionline that propagates the communication signals.
 24. The arrester ofclaim 21 where the MOV comprises one or more fins.
 25. The arrester ofclaim 21 comprising a first MOV and a second MOV separated by aninsulator.
 26. The arrester of claim 25 of the first MOV is connected toa center conductor of a coaxial interface and the second MOV isconnected to a shield conductor of the coaxial interface.
 27. Thearrester of claim 25 where the first MOV and the second MOV areconcentric to each other.
 28. The arrester of claim 25 where the firstMOV and the second MOV are at least one of coplanar with each other orarranged in a twisted pair.
 29. The arrester of claim 25 where thearrester is connected to the surface wave launcher, which includes acoupler and a reflector, and where the first MOV is connected to thecoupler and the second MOV is connected to the reflector.
 30. Thearrester of claim 25 where the first MOV and the second MOV areencompassed by a single body.
 31. The arrester of claim 25 where each ofthe first MOV and the second MOV has a respective external body.
 32. Thearrester of claim 31 where each of the external bodies includes at leastone fin.
 33. A device configured for interposition between a networkunit that processes data communications signals and a surface wavelauncher that surrounds a high power transmission line and launches thecommunication signals on, and receives the communications signals fromthe high power transmission line, the device including at least onearrester comprising an RC network of resistors and capacitors surroundedby an insulator, the at least one arrester preventing voltage fromarcing from the power transmission line to the network unit, and alsocapable of propagating the communications signals between the networkunit and the surface wave launcher.
 34. The device of claim 33 where thenetwork of resistors and capacitors forms a biasing ladder.
 35. Thedevice of claim 33 where each at least one arrester comprises a metaloxide varistor (MOV).
 36. The device of claim 33 where each at least onearrester comprises a coaxial transmission path for the communicationssignals.
 37. The device of claim 33 having a first arrester and a secondarrester separated by the insulator.
 38. The arrester of claim 37 wherethe first arrester and the second arrester are concentric to each other.39. The arrester of claim 37 where the first arrester and the secondarrester are at least one of coplanar with each other or arranged in atwisted pair.
 40. The arrester of claim 37 where the first arrester isconnected to a center conductor of a coaxial interface and the secondarrester is connected to a shield conductor of the coaxial interface